## 1. Introduction

In recent years, scientific research regarding electric machines has been strongly directed towards the adoption of multi-phase winding configurations, thanks to the many advantages over conventional three-phase topologies, such as fault-tolerance, lower harmonic currents and torque ripple [

1,

2,

3,

4]. Moreover, adopting slightly asymmetrical winding configurations represents a valuable element during the early stage of the electric machine design, that can bring several advantages in different application fields [

5,

6,

7,

8]. It is well known that, historically, winding configurations with slight asymmetries were only used for pole-changing machines [

9,

10] or for motors with Pole Amplitude Modulation (PAM) [

11]. Nevertheless, recent advances have demonstrated that asymmetrical winding configurations may offer a significant performance improvement by increasing the number of possible slot/pole combinations, while keeping comparable performances to traditional machines. It is worthwhile noting here that even symmetrical windings, once fabricated, present slight asymmetries due to manufacturing tolerances. It has also been demonstrated that a careful use of asymmetries may even serve to improve motor performances by reducing the effects of slot harmonics [

12]. Moreover, the exact knowledge of the differential leakage factor, namely

${\sigma}_{0}$, is a crucial aspect for the adequate characterization of an electrical machine during the design stage, because it represents a valuable parameter influencing some of the performances of the machine itself. In this context, we suggest extended mapping in terms of the unbalance degree and the leakage factor for both single-layer and double-layer multiphase symmetrical and asymmetrical winding configurations of rotating electrical machines. This mapping can be a useful tool for the designer with the aim of choosing the optimal combination between the slot/poles ratio and the number of phases during the design stage of the related winding, even with a slightly asymmetrical configuration. More in detail, the proposed investigation is extended to electrical machines whose layer number

y ranges from 1 (single-layer) to 2 (double-layer), the slots number

N from 20 to 60, the pole pairs number

p is from 1 to 15 and the number of phases

m from 3 to 6, exploring almost 10,000 values of unbalance degree and differential leakage factor. This paper is organized as follows: the definition of the symmetry winding conditions, of the unbalance degree and the investigation of its variability is reported in

Section 2.

Section 3 describes the general formula for the determination of the differential leakage factor in

m-phase motors.

Section 4 reports and discusses the obtained mapping for all the analyzed winding configurations; finally, the finite element validation is proposed in

Section 5.

## 2. Symmetry Conditions and Degree of Unbalance in m-Phase Machine
Windings

Considering a generic

m-phase electrical machine winding with

N slots,

y-layers and

p pole pairs, a set of general symmetry conditions can be easily introduced [

13,

14].

Let

t, the number of repetitions of the elementary winding:

and

$\eta $ the number of empty slots. The number of slots per phase per repetition can be defined as:

The first symmetry condition follows:

Moreover, naming

$\gamma $ as

where

$\mathbb{N}$ is the set of natural numbers, whereas $\eta $ represents the number of empty (unfilled) slots.

The winding is defined as symmetrical if, and only if, conditions (

5) and the first of Equation (

3) are satisfied. On the contrary, the winding is defined as asymmetrical.

Moreover, the definition of the degree of unbalance

$D.U.$% is given by the following formula:

where

${k}_{wpd}$ is the direct component of the winding factor at the

pth harmonic, whereas

${k}_{wpi}$ is the inverse component of the winding factor at the

pth harmonic. These components and the related phases for the

hth phase can be computed as follows [

13,

15,

16]:

and

where

where

$\nu $ is the generic harmonic order,

$h=1$ ...

m is the

hth winding phase and the

${a}_{h,n}$ are the slot emf coefficients, which can be computed by referring to [

13]. If the winding is symmetrical, the computation of harmonic winding factors can be limited to only one phase (for example, the 1st phase—i.e.,

$h=1$). If

$D.U.\%$ is less than 5%, the winding can be classified as slightly asymmetrical.

The variability of the unbalance degree in polyphase machines can be investigated by applying Equation (

6), computed through the ACWIND Software [

16], for different winding configurations in terms of number of slots, pole pairs, phases and number of layers. More in detail, these parameters have been varied according to

Table 1, reaching 4800 combinations, which are graphically summarized in

Figure 1.

This range of variability has been selected in order to cover the most common base winding configurations, both symmetrical and asymmetrical. The values of $D.U.\%$ are also classified as a function of the number of phases and number of layers. From these graphs, it appears clear that the adoption of slightly asymmetrical windings allows a higher possibility of choices with regard to the slot-poles combinations. Indeed, almost 96% of the examined combinations can be theoretically considered between symmetrical (18%) and slightly asymmetrical (76%) configurations. Moreover, the range of symmetrical combinations decreases for increased values of m, while, as m increases, the possibility of asymmetrical configurations increases up to 500 combinations. The results regarding the four-phase configuration, even if reported in the previous graphs, should not be considered due to their low practical utility.

## 3. The Differential Leakage Factor in m-Phase Machine Windings

It is well known that the differential leakage factor, namely

${\sigma}_{0}$, is a valid parameter for the characterization of an electrical machine during its early design stage. However, the exact determination of

${\sigma}_{0}$, especially for multiphase asymmetrical machines, could be very troublesome [

11,

17,

18]. Recently, the authors have proposed a general procedure that simplifies its exact computation by adopting the Goerges polygon [

19,

20]. Generally,

${\sigma}_{0}$ is defined as follows [

11,

18,

20,

21,

22,

23,

24]:

where

${W}_{p}$ is defined as the magnetic energy at the working harmonic, whereas

${W}_{\delta}$ represents the magnetic energy in the air-gap, which can be expressed by the following formula:

where

${\mu}_{0}$ is the permeability of vacuum,

${l}_{i}$ is the ideal axial length of the machine,

$\tau $ is its pole pitch,

${v}_{i}$ is the instantaneous value of air-gap MMF at a generic

ith slot and

${\delta}^{\u2033}$ is the fictive air-gap length, given by:

where

${k}_{C}$ is the Carter factor,

${k}_{sat}$ is the saturation factor and

$\delta $ is the air-gap length.

The energy

${W}_{p}$ can be expressed as follows:

where

Finally,

${\sigma}_{0}$ is given by:

${V}_{p}$ is defined as follows:

where

w is the number of series-connected coil turns per phase and

${k}_{wp}$ is the winding factor at the working harmonic (

$\nu =p$). Finally,

I and

${I}_{x}$ are the

$rms$ and peak values of the sinusoidal phase current, respectively.

It must be underlined that symmetrical Goerges polygons lead to constant leakage factor, independently from the slot number taken into account. On the contrary, asymmetrical polygons (to which correspond, in the majority of cases, asymmetrical winding configurations) lead to temporal variability of the leakage factor. For the latest case, the mean leakage factor all over the electric period is considered. In addition, this analysis is carried out by imposing a symmetrical system of supply currents.

## 4. Results and Discussion

This section presents an extended mapping for the fast estimation of both $D.U.\%$ and ${\sigma}_{0}$ in a $N-p$ plane, providing a useful tool for the designers in the early design stage of electric machine windings.

A first result to be discussed is reported in

Figure 2a, which provides the mapping in a

$N-p$ plane of all the possible double-layer symmetrical configurations for

m ranging between 3 and 6. As expected, it can be noticed that several

$N-p$ combinations are symmetrical for any number of phases (e.g.,

$N60-p1$,

$N60-p7$, etc.), whereas other slot-poles combinations are symmetrical for only a specific

m (

$N21-p1$ only for

$m=3$,

$N20-p2$ only for

$m=5$ and so on). In addition,

Figure 2b summarizes the distribution in the

$N-p$ plane of asymmetrical configurations with

$D.U.>5\%$. It can be noticed that the intensification of these configurations is detected for a low number of slots. The latest mapping could be useful for the designer in order to avoid the

$N-p-m$ combinations that provide high unbalances in the winding. It appears evident that the solutions not included in

Figure 2a,b correspond to the

$N-p-m$ combinations of slightly asymmetrical windings. Therefore, the simultaneous analysis of the two mappings can help the designer to choose the optimal solution in terms of slot/poles ratio.

Another significant result is in

Figure 3, comparing the mapping, in the

$N-p$ plane, of the leakage factors for all proposed double-layer and single-layer combinations. In this case, the mapping is limited to values of leakage factor confined within 20%. Firstly, for all graphics, a region with a low value of

${\sigma}_{0}$ can be identified, mainly corresponding to areas with a low number of pole pairs. This region appears more confined and less uniform for single-layer winding configurations. Secondly, for each graph, some intensification regions can be detected, as shown by the red areas plotted in the same Figure, corresponding to the

$N-p-m-y$ winding configurations with a value of

${\sigma}_{0}$ close to 20%. Furthermore, the white region corresponds to all the

$N-p$ combinations with

${\sigma}_{0}>20\%$, which should be avoided by the designer. All the plotted graphics are also integrated with the possible symmetrical configurations of the specific phase taken into account (red dots).

Finally,

Figure 4 reports the mapping of all the possible valuable configurations with a leakage factor

$<20\%$ and a

$D.U.\%<5\%$ for all proposed phase numbers. This comparison leads to the fact that the five-phase configuration provides a higher choice of possibilities in terms of

$N-p$ combination.

In conclusion, it can be stated that the graph of

Figure 4 can be used by the designer as an aid for choosing a suitable combination of slots, poles and phases minimizing the related leakage factor. On the contrary, it appears clear that the

$N-p-m$ combinations corresponding to relevant peaks of

${\sigma}_{0}$ should be avoided by the designers.

In order to provide a practical example of the proposed approach, a five-phase, double-layer winding located into 45 slots of a 10 poles machine is taken into account. The mapping of

Figure 3c and the overview of

Figure 4 demonstrate the feasibility of its design in terms of both degree of unbalance and leakage factor, allowing for their fast estimation and avoiding complex computations. Indeed, according to (

6) and (

16), the configuration has a slight asymmetry (

$D.U.\%$ is equal to 0.4%) and

${\sigma}_{0}$ is equal to 11.44%, obtained by means of the Goerges polygon plotted in

Figure 5 [

25,

26]. The related winding scheme and the spatial distribution of the Magneto Motive Force (MMF) are plotted in

Figure 6 and

Figure 7, respectively.

A dual three-phase, double-layer winding located into 36 slots of a 4 poles machine is considered as a second practical example. As well as for the previous case, according to the mapping of

Figure 3e and

Figure 4, this winding configuration, whose layout scheme is depicted in

Figure 8, can be assumed as feasible. According to (

6) and (

16), the winding configuration is slightly asymmetrical and

${\sigma}_{0}$ is equal to 1%. The corresponding Goerges polygon is plotted in

Figure 9, whereas the spatial distribution of the Magneto Motive Force is depicted in

Figure 10. As previously reported, the proposed mapping of both

$D.U.\%$ and

${\sigma}_{0}$ can help the designer for the fast estimation of crucial parameters involved during the design stage of electrical machines.

## 5. Finite-Element Validation

The Finite-Element Method (FEM) is used to demonstrate the validity of the obtained values of the mean leakage factors for the winding configurations taken into account in the previous sections. More in detail, the FEMM4.2 software is adopted in order to carry out the finite element models of four Interior Permanent Magnet Synchronous Motors (IPMSMs), which mainly differ for the number of slots (equal to 24, 27, 30 and 33). For each of the 6-poles model, the number of phases has been varied from 3 to 6, reaching 16 models with different combinations between N and m.

Afterwards, the angular position of the rotor has been varied from

$0{}^{\circ}$ to

$360{}^{\circ}$ with steps of

$10{}^{\circ}$, obtaining 37 simulations for each model and almost 600 overall simulations.

Figure 11 shows an example of the simulation results, in terms of flux density plot, achieved from the FEM analysis. Moreover, the variability over an entire electrical cycle of the leakage factor, computed both with FEM and with (

16), for configurations with asymmetrical and symmetrical Goerges polygons, are depicted in

Figure 12 and

Figure 13, respectively. In any of the proposed cases, the comparison between the computed leakage factors and the FEM results confirms the validity of the reported

${\sigma}_{0}$ values.