High-Capacity Multiple-Input Multiple-Output Communication for Internet-of-Things Applications Using 3D Steering Nolen Beamforming Array ^†

Abstract

In this paper, a novel 2D Nolen beamforming phased array with 3D scanning capability to achieve high channel capacity is presented for multiple-input multiple-output (MIMO) Internet-of-Things (IoT) applications. The proposed 2D beamforming phased array is designed by stacking a fundamental building block consisting of a 3 × 3 tunable Nolen matrix, which applies a small number of phase shifters with a small tunning range and reduces the complexity of the beam-steering control mechanism. Each 3 × 3 tunable Nolen matrix can achieve a full 360° range of progressive phase delay by exciting all three input ports, and nine individual radiation beams can be generated and continuously steered on azimuth and elevation planes by stacking up three tunable Nolen matrix in horizontal and three in vertical to maximize signal-to-noise ratio (SNR) in the corresponding spatial directions. To validate the proposed design, the simulations have been conducted on the circuit network and assessed in a fading channel environment. The simulation results agree well with the theoretical analysis, which demonstrates the capability of the proposed 2D Nolen beamforming phased array to realize high channel capacity in MIMO-enabled IoT communications.

1. Introduction

The emerging 5G/NextG and Wi-Fi 6E/7 have revolutionized wireless communication technology, and they feature high channel capacity, reduced transmission latency, and reduced network congestion. With the new wide instantaneous band spectrum, a novel architectural radio access network, improvements in channel model estimation and physical layer technologies, smart antenna design, beamforming algorithms, and massive multiple-input-multiple-output (MIMO) techniques are investigated to meet a high standard requirement in the upgraded Internet-of-Things (IoT) network [1,2,3]. Specifically, in comparison with conventional single-input single-output and single-input multiple-output (SIMO or MISO) systems, the MIMO technique significantly improves the channel capacity to satisfy the demand for high data rate transmission, and it is widely applied in IoT applications, including smart transportation, smart healthcare, smart industry, and smart cities [4,5]. To further enhance the selection diversity capacity and maximize the spatial efficiency and channel signal-to-noise ratio (SNR), the beamforming technique is developed in an MIMO system as a useful pre-coding approach [6,7]. Digital beamforming, local oscillator phase shifting, and RF phase shifting are the primary techniques used to realize beamforming in the MIMO system, where the radiation beam formed from an antenna array system can be continuously steered to the desired direction. Unlike other beamforming methods, in the RF phase shifting technique, controlling the signal phase and magnitude for radiating antenna elements is crucial to manipulating the spatial angle of beamforming, and several methods have been investigated, such as parallel feeding [8,9], series feeding [10,11], and matrix feeding [12,13,14], to control the signal phase and magnitude. Compared with the other two, the matrix feeding network is composed of couplers, phase shifters, crossover, and a power splitter, which performs as a spatially fast Fourier transform to radiate up to N orthogonal directive beams combined with a uniform linear antenna array. More specifically, the Butler matrix is one of the most well-known feeding networks, and it has been intensively investigated in terms of symmetrical or unsymmetrical topology with different scales in [15,16] and tuning capability in [17,18]. With the increasing number of antenna elements in an RF beamforming phased array, the RF front-end needs to integrate a smaller number of passive components, such as a coupler, crossover, delay line, and phase shifter, in the feeding network to minimize power loss and simplify the system topology, especially for mm-wave and THz communications. Compared with other feeding networks, the Nolen matrix is composed of fewer circuit components, resulting in low power loss, compact size, and flexibility to generate an arbitrary number of radiation beams, which is an optimum candidate for large-scale RF beamforming phased arrays. In a previous study [19], the Nolen matrix was investigated to generate flexible beams and reduce their size. However, all of them focused on fixed radiation beams without any scanning capabilities, which limits the spatial diversity and efficiency of MIMO systems.

In this paper, a novel 2D tunable Nolen matrix, as shown in Figure 1, has been proposed to generate and steer radiation beams in a full 3D spatial domain for next-generation spatial and beam–space multiplexing wireless applications. The proposed 3D beamforming Nolen phased array features are as follows: (1) flexible progressive phase difference in horizontal and vertical antenna arrays; (2) phase shifters with a small tuning range (120°) are used to realize full 360° progressive phase difference in two planes; (3) only two-channel voltages are applied to concurrently control beam steering; and (4) 3D cubic space coverage enables further enhancement of system channel capacity.

The work in this paper is an extension of our previous publication [20]. The major new contributions to this paper are as follows:

• A 3D beamforming MIMO system is established based on the 2D Nolen matrix phased array, including modeling of the communication channel and Nolen matrix network. Then, its capability of enhancing channel capacity has been demonstrated.
• The advancements of the proposed 3 × 3 tunable Nolen matrix are more deeply discussed and compared to other works on tunable beamforming networks.

2. Design Theory and Analysis

The proposed 3D beamforming MIMO communication is depicted in Figure 1, where a novel tunable Nolen matrix beamforming phased array is applied both on the transmitter and receiver sides with a nine-element antenna array. Each of them is designed by stacking three tunable Nolen matrices in the y axis and another three along the x axis. Applying signals at one port, the equal magnitude and progressive phase delay (β_x, β_y) in two dimensions are generated fed into the nine-element antenna array to generate radiation beams in the cubical 3D space. Nine unique radiation beams pointing in the corresponding cubic sectors can be generated by switching different input ports. Furthermore, to fully cover the 3D space in each sector or steer the beam in any direction, two-channel voltages are applied to configure all of the phase shifters embedded in the Nolen matrix that simultaneously generate progressive phase differences (β_x, β_y) within the 360° range at their output ports.

2.1. Model of the Proposed 3D MIMO System

Our proposed MIMO system is composed of a receiving diversity scheme, with nine transmitting antennas (N_T = 9) and nine receiving antennas (N_R = 9). Assuming the channel fades at each receiving branch is frequency nonselective and slowly changes, then the received signal at the individual diversity branch is modeled as follows:

$$r_{i,k}=h_{i,k}\cdot s+n_{i,k}$$

(1)

where {i, k|1 ≤ i, k ≤ N_R}, s is the transmitted signal, H = [h_1,1, …, h_i,k] is the channel coefficient, and n = [n_1,1, …, n_i,k] is the additive white Gaussian noise with identical power spectral density per dimension. If two 2D Nolen matrixes with the transfer functions B_T and B_R (B_T = B_R = B) are inserted to feed the antenna elements at each side, the received signal at the diversity branch (i, k) can be given as follows:

$$r_{i,k}=h_{i,k}^{*}\cdot s+n_{i,k}^{*}$$

(2)

where $h_{i,k}^{*}$ and $n_{i,k}^{*}$ are effective vectors of channel and noise matrix. Then, entries of the single 3 × 3 Nolen matrix w are given as follows:

$$w_{m,n}={\alpha }_{m,n}\cdot e^{j{\phi }_{m,n}}=\frac{1}{\sqrt{N}}\cdot {[e^{j[2\pi (n-1)/N]}]}^{m-1}\cdot {[e^{j(r\cdot \pi )}]}^{m-1}$$

(3)

where m, n ϵ [1, N] (N = 3) index the input and output ports of the circuit matrix, and r is the phase ratio. From the matrix generated by Equation (3), the phase response is determined by the value of r with a fixed dimension number N. The phase difference between the matrix elements along the same row or column can also be manipulated, which corresponds to the progressive phase differences of the beamforming matrix.

Table 1. Examples of progressive phase differences with different phase ratio r.

Phase Differences in 3 × 3 Nolen Matrix	Example 1 (r = 0)	Example 2 (r = 0.5)
Δϕ1 = φ1,n − φ1,n−1	0°	+90°
Δϕ2 = φ2,n − φ2,n−1	+120°	+30
Δϕ3 = φ3,n − φ3,n−1	−120°	−150°

shows two examples that validate the nature of a tunable 3 × 3 Nolen matrix. When r = 0, the progressive phase differences are 0°, +120°, and −120°, respectively. When r = 0.5, the progressive phase differences are +90°, +30°, and −150°, respectively.

For a 2D Nolen beamforming matrix, the entries can be further analyzed by including the transfer function of two stage matrices. Presuming a, b ϵ [1, N] are the dimensions of Nolen matrices on the second stage, the transfer function B is revised into a matrix with a dimension of N_T × N_R, and the entries of the entire 2D beamforming network are expressed as follows:

$$B=B_{(m\cdot n),(a\cdot b)}=w_{n,b}^x\cdot w_{m,a}^y$$

(4)

where {m, n, a, b | 1 ≤ (m, n, a, b) ≤ N}, and the superscript x and y denote the Nolen matrix at the first and second stages for tuning progressive phase along the x axis and y axis, respectively, such that the received signal in Equation (2) can be further derived as follows:

$$\begin{array}{ll}{r}_{m,a}& =h_{m,a}^{*}\cdot s+n_{m,a}^{*}\\ & ={\displaystyle \sum _{n=1}^N\left[w_{m,n}^x\cdot {\displaystyle \sum _{b=1}^N{w}_{a,b}^y}\right]}\cdot h_{m,a}\cdot s+{\displaystyle \sum _{n=1}^N\left[w_{m,n}^x\cdot {\displaystyle \sum _{b=1}^N{w}_{a,b}^y}\right]}\cdot n_{m,a} \end{array}$$

(5)

To realize the proposed full-coverage 3D beamforming phased array, a novel 2D tunable Nolen beamforming matrix was designed accordingly.

2.2. Design of 2D Tunable Nolen Matrix Beamforming

The fundamental building block tunable 3 × 3 Nolen matrix is a microwave network with three input ports (P₁–P₃) and three output ports (P₄–P₆), as shown in Figure 2. It is composed of three couplers with two different coupling ratios, C₁ and C₂, three tunable phase shifters (L₂, L₃, and L₄) with a phase tuning range of ϕ₂, ϕ₃, and ϕ₄, and one fixed phase shifter, L₁ (phase delay = ϕ₁). More specifically, when port P_α of coupler 1 is excited, the signal at the coupling port is C₁, and the phase delay is ϕ_α,C1. While the signal at the through port has a magnitude of (1-C₁) and a phase delay of ϕ_α,T1. Similarly, when P_β is excited, the same magnitude distributions can be achieved, while the phase delays of ϕ_β,C1 and ϕ_β,T1 are obtained, respectively. For the other two couplers with a coupling ratio of C₂, the corresponding magnitudes and phase delays under different port excitations are shown in Figure 2 as well. More details about coupler design have been addressed in the previous work [21]. In this design, the phase differences of couplers under different port excitations can be expressed as follows:

$$({\varphi }_{\alpha ,C1}-{\varphi }_{\alpha ,T1})+({\varphi }_{\beta ,C1}-{\varphi }_{\beta ,T1})=\pi$$

(6)

$$({\varphi }_{\alpha ,C2}-{\varphi }_{\alpha ,T2})+({\varphi }_{\beta ,C2}-{\varphi }_{\beta ,T2})=\pi$$

(7)

Also, the corresponding coupling rations C₁ and C₂ are derived, respectively, to 2/3 and 1/3 by considering the requirement of equal magnitude distribution and progressive phase differences across the entire matrix. Therefore, the S parameters of the 3 × 3 network are decently derived as follows:

$$S_{41}=\frac{\sqrt{3}}{3}{e}^{j{\varphi }_{\alpha , T1}}$$

(8)

$$S_{51}=\frac{\sqrt{3}}{3}{e}^{j({\varphi }_{\alpha , T2} + {\varphi }_{\alpha , C1} - {\varphi }_3)}$$

(9)

$$S_{61}=\frac{\sqrt{3}}{3}{e}^{j({\varphi }_{\alpha , C1} + {\varphi }_{\alpha , C2} - {\varphi }_3- {\varphi }_4)}$$

(10)

$$S_{42}=\frac{\sqrt{3}}{3}{e}^{j({\varphi }_{\alpha , T1} + {\varphi }_{\beta , C1} - {\varphi }_1)}$$

(11)

$$S_{52}=\frac{\sqrt{12}}{12}{e}^{j({\varphi }_{\beta , T1} + 2 {\varphi }_{\alpha , T2} - {\varphi }_1- {\varphi }_3)} + \frac{1}{2}{e}^{j({\varphi }_{\alpha , C2} + {\varphi }_{\beta , C2} -{\varphi }_2)}$$

(12)

$$S_{62}=\frac{\sqrt{12}}{12}{e}^{j({\varphi }_{\beta , T1} + {\varphi }_{\alpha , T2} + {\varphi }_{\alpha , C2} - {\varphi }_1- {\varphi }_3 - {\varphi }_4)} + \frac{1}{2}{e}^{j({\varphi }_{\beta , T2} + {\varphi }_{\alpha , C2} -{\varphi }_2 -{\varphi }_4)}$$

(13)

$$S_{43}=\frac{\sqrt{3}}{3}{e}^{j({\varphi }_{\beta , C1} + {\varphi }_{\beta , C2} - {\varphi }_1)}$$

(14)

$$S_{53}=\frac{\sqrt{12}}{12}{e}^{j({\varphi }_{\beta , T1} + {\varphi }_{\alpha , T2} + {\varphi }_{\beta , C2} - {\varphi }_1- {\varphi }_3)} + \frac{1}{2}{e}^{j({\varphi }_{\beta , T2} + {\varphi }_{\beta , C2} -{\varphi }_2)}$$

(15)

$$S_{63}=\frac{\sqrt{12}}{12}{e}^{j({\varphi }_{\beta , T1} + {\varphi }_{\beta , C2} + {\varphi }_{\alpha , C2} - {\varphi }_1- {\varphi }_3 - {\varphi }_4)} + \frac{1}{2}{e}^{j(2{\varphi }_{\beta , T2} -{\varphi }_2 -{\varphi }_4)}$$

(16)

For the excitation of each input port, conditions such as equal magnitudes, progressive phase distributions, and unique phase differences are required to steer the radiation beam in its dedicated sector. To satisfy the required conditions, the fixed and tunable phase shifters are derived as follows:

$${\varphi }_2-{\varphi }_4-{\varphi }_1={\varphi }_{\beta ,C2}-{\varphi }_{\beta ,C1} \mp 90°$$

(17)

$${\varphi }_3-{\varphi }_4=({\varphi }_{\alpha ,C1}-{\varphi }_{\alpha ,T1}) - ({\varphi }_{\alpha ,C2}-{\varphi }_{\alpha ,T2}) +{\varphi }_{\alpha ,T2}$$

(18)

Then, by substituting Equations (17) and (18) into (8)–(16), the progressive phase differences of the proposed tunable 3 × 3 Nolen matrix are obtained as follows:

$$\Delta {\beta }_1= ({\varphi }_{\alpha ,C2}-{\varphi }_{\alpha ,T2}) -{\varphi }_4$$

(19)

$$\Delta {\beta }_2= ({\varphi }_{\alpha ,C2}-{\varphi }_{\alpha ,T2}) \pm 120°-{\varphi }_4$$

(20)

$$\Delta {\beta }_3= ({\varphi }_{\alpha ,C2}-{\varphi }_{\alpha ,T2}) \mp 120°-{\varphi }_4$$

(21)

where Δβ_i denotes the progressive phase differences among the output ports when applying the incident wave from port 1 to port 3 of the 3 × 3 Nolen matrix, respectively. It is observed that Δβ_i is determined by ϕ_α,C2 − ϕ_α,T2 (phase difference of coupler 2) and phase delay ϕ₄. For a given coupler, ϕ_α,C2 − ϕ_α,T2 is a pre-determined constant value. With this fact, it is easy to find that tuning the phase (ϕ₄) of the phase shifter L₄ will enable continuous progressive phase difference changes in the proposed matrix. From (19) to (21), Δβ_i features a 120° offset from each other under each input port excitation (i.e., Δβ₂ − Δβ₁ = Δβ₃ − Δβ₂ = Δβ₁ − Δβ₃ = ± 120°), which further reduces the required tuning range of the tunable phase shifter L₄ from 360° to 120°, without decreasing the full-coverage range of 360°. In addition, the ϕ₂ and ϕ₃ tunable phase shifters must follow the change in ϕ₄ with the same value or a fixed offset, which would reduce the complexity of the control method in the proposed beamforming phased array.

From the analysis above, the couplers in the proposed 3 × 3 tunable Nolen matrix are designed based on our previous work [21]. After the couplers are determined, the phase differences in each coupler (ϕ_α,C1 − ϕ_α,T1 & ϕ_α,C2 − ϕ_α,T2) can be accordingly obtained, and the phase shifters L₁, L₂, L₃, and L₄ can be derived by applying (17)–(18).

To achieve continuous phase tuning with simplified control, a tunable transmission line, as in our previous work [22], has been applied to design tunable phase shifters. It consists of two identical microstrip lines in series and three short-end varactors at two ends and the center. Here, an MA46H120 varactor is adopted as the tunable capacitor, and phase tuning is controlled by two bias voltages. Two proposed phase shifters are cascaded to implement the tunable phase shifters (L₂, L₃, and L₄ in Figure 2), where the phase tuning range is 120° within low loss variation.

2.3. 2D Phased Array for Full-Coverage Beamforming

To realize full-coverage 3D beamforming, six proposed 3 × 3 tunable Nolen matrices are stacked and cascaded to form a 2D antenna feeding network. From Figure 1, three tunable Nolen matrices are installed on the x axis, while the other three are on the y axis. Therefore, there are nine input and nine output ports in this feeding network, and the output ports are connected to a 2D patch antenna array. The array factor (AF) of a planar P × Q antenna array that is excited by incident waves of identical magnitude is derived as follows:

$$A{F}_{P \times Q}={\displaystyle \sum _{p=1}^P{e}^{j(p-1)(k\cdot dx\cdot \sin \theta \cos \varphi + {\beta }_x)}}\cdot {\displaystyle \sum _{q=1}^Q{e}^{j(q-1)(k\cdot dy\cdot \sin \theta \sin \varphi + {\beta }_y)}}$$

(22)

where v is the wavenumber, dx and dy are the distance between the adjacent antenna elements along the x and y axes, β_x and β_y are progressive phase differences between the adjacent antenna elements on the x and y axes, and θ and ϕ are the radiation beam angles on elevation and azimuth dimensions, respectively. The radiation angle of the main beam in two dimensions can be derived from the following equations:

$$v\cdot dx\cdot \sin \theta \cdot \cos \varphi +{\beta }_x=0$$

(23)

$$v\cdot dy\cdot \sin \theta \cdot \sin \varphi +{\beta }_y=0$$

(24)

By exciting nine different input ports P₁–P₉, the progressive phase differences in the proposed 2D tunable Nolen matrix feeding network on x and y axes (β_x and β_y) are found, as listed in

Table 2. Progressive phases and selection of radiation sector under applied input ports.

Port Excitation	Progressive Phase (βx, βy)	Radiation Sector
1	(−90°, −90°)	Sec. 1
2	(−90°, 30°)	Sec. 2
3	(−90°, 150°)	Sec. 3
4	(30°, −90°)	Sec. 4
5	(30°, 30°)	Sec. 5
6	(30°, 150°)	Sec. 6
7	(150°, −90°)	Sec. 7
8	(150°, 30°)	Sec. 8
9	(150°, 150°)	Sec. 9

. Specifically, there is a 120° phase separation between each set of β_x,y by exciting the input port in sequence. β_x and β_y both have an independent tuning range of 120°. Based on (23) and (24), the main beams point toward nine unique directions in 3D space, and each beam in the cubic sector can be further steered by controlling tunable phase shifters.

3. Experimental Results and Discussion

To verify the theory of the proposed 2D tunable Nolen matrix and 3D beamforming, the simulation was conducted using Keysight ADS (Santa Rosa, CA, USA). A 5.8 GHz tunable 3 × 3 Nolen matrix was designed and fabricated on Rogers RT/Duroid 6002 laminate (Chandler, AZ, USA), which has a thickness of 0.508 mm, a tanδ of 0.0012, and a dielectric constant ε_r = 2.94, 6

3.1. S Parameter of 3 × 3 Tunable Nolen Matrix

In the simulation results, all output ports experience an ideal insertion loss of 9.54 dB at a center frequency of 5.8 GHz. As shown in Figure 3, the progressive phase differences are plotted in both x and y dimensions (β_x and β_y) for excitations of nine input ports, where the solid and dash lines denote the limits of phase tuning range (Δβ = 120° contributed from the tunable phase shifters), and blue and red curves indicate progressive phase differences along the x and y axes. In Figure 3a, for excitation on input port P₁, the progressive phase differences between the two adjacent outputs are tuned between −90° and −210° in both dimensions. In Figure 3b, for input port P₂, β_x is tuned from −210° to −90°, while β_y is tuned from −90° to 30°. In Figure 3c, for input port P₃, β_x keeps the same tuning range while β_y is tuned from 30° to 150°. It is observed that the excitations on ports along the vertical axis result in an increase of β_y (from −210° to 150°), which totally covers the full range of progressive phase differences. On the other hand, for the ports along the horizontal axis (i.e., P₁, P₄, and P₇), β_x is tuned from −210° to 150° with no change in β_y. Therefore, by exciting the nine input ports (P₁ to P₉) and tuning the phase shifters, the beam can be radiated in a full 3D space.

3.2. 3D Beamforming

Based on the analysis above, our proposed 2D tunable Nolen matrix enables generating radiation beams in 3D space. In specific, by sequentially exciting the nine input ports, the corresponding radiation sectors can be selected, and the radiation beams in that sector can be continuously steered within the cubic region by tuning the phase shifters. As shown in Figure 4, the radiation beam with normalized gain within each sector is plotted on azimuth (Az) and elevation (El) dimensions. The specified coordinates are simulated based on the Equations (18) and (19). For example, when the input port P₅ is excited, the radiation beam is generated within the region of the center sector, and it can be radiated to any angle in that cubic region. Here, in Figure 4, four beams in a clockwise direction, (28°, 45°), (28°, 135°), (28°, 225°), and (28°, 315°), are shown to demonstrate our design concept. Similarly, any radiation beam angle within their dedicated sectors can be generated by tuning phase shifters embedded in the proposed design.

3.3. Evaluation of the Proposed Beamfomring MIMO Channel Capacity

The system channel capacity is evaluated for the proposed 2D Nolen beamforming phased array by applying the Shannon’s formula and equation effective channel matrix H*. The optimum MIMO capacity with the proposed 3D coverage phased array can be expressed as follows:

$$\begin{array}{ll}C& ={\log }_2\left[\det \left\{\gamma \cdot H^{*}\cdot {(H^{*})}^H\right\}\right]\\ & ={\log }_2\left[\det \left(\gamma \cdot \{B_{Rx}^H\cdot H\cdot B_{Tx}\}\cdot \{B_{Tx}^H\cdot H^H\cdot B_{Rx}\}\right)\right]\end{array}$$

(25)

where γ denotes the signal-to-noise ratio (SNR) along the individual diversity branch, and [·]^H indicates transpose conjugate. Figure 5 shows the simulation results of the system capacity of the proposed MIMO system versus SNR. Compared with the scheme of 1 × 9 SIMO (or MISO) system and the normal 9 × 9 MIMO system, our proposed 9 × 9 MIMO system provides a higher signal power and offers significantly larger capacity benefits with higher SNR levels.

To verify the design concept, a fundamental tunable 3 × 3 Nolen matrix block operating at 5.8 GHz is designed and fabricated on Rogers RT/Duroid 6002 laminate (Figure 6), which has 0.508 mm thickness, 0.0012 loss tangent, and 2.94 dielectric constant. The overall size of the tunable Nolen matrix is about 113.59 mm × 34.25 mm, which equals 2.19 λ × 0.66 λ (λ: wavelength at 5.8 GHz), as shown in Figure 6. It includes a tunable Nolen matrix, a 1 × 3 Vivaldi antenna array, and a DC control circuit. In future work, more details about the measured results of the proposed 3D beamforming array and system level evaluations are needed. Additionally, further investigations on multi-band/wideband tunable Nolen matrix beamforming phased arrays will be conducted to further optimize their capabilities in high-capacity MIMO IoT communications.

Here, in

Table 3. Comparison between a 2D tunable Nolen matrix phased array and other beamforming networks.

	[7]	[9]	[17]	[18]	This work
Antenna Feed Type	Parallel	Parallel	Butler matrix	Butler matrix	Nolen matrix
Components Integration	Phase shifter, power divider, and amplifier	Divider, lumped element, and phase shifter	Coupler, power divider, and phase shifter	Coupler, crossover, and phase shifter	Coupler and phase shifter
MIMO Scale	4 × 4	N.A.	4 × 4	4 × 4	9 × 9
Scanning Dimension	2D	2D	2D	2D	3D
Frequency (GHz)	28	2.5	2.45	2.4	5.8
Phase Shifters Number	4	4	8	6	3
Shifting Type	Switching	Continuous	Switching	Continuous	Continuous
Phase Shifting (°)	180	90	142	360	120
Progressive Phase (°)	360	360	324	360	360
DC Control Units	4	7	8	6	2

, the proposed 2D tunable Nolen matrix phased array has been compared to other MIMO beamforming networks for IoT communications. It can be observed that the proposed design achieves a flexible 3D beam-steering capability and larger MIMO scales to optimize the channel capacity. Also, it features a simplified circuit topology with minimum control units and requiring minimized phase tuning range to achieve a full 360° progressive phase.

4. Conclusions

In this paper, a high channel capacity MIMO wireless communication using a 2D Nolen beamforming array with 3D scanning capability is presented. The 2D beamforming phased array is designed by stacking a fundamental building block consisting of a 3 × 3 tunable Nolen matrix. By exciting nine individual input ports of the phased array, the corresponding radiation beams can be generated and continuously steered on both azimuth and elevation planes to maximize the signal-to-noise ratio (SNR) in the corresponding spatial directions. The simulations have been conducted on both the front-end aspect and the entire system to verify the design theory, and the results demonstrate that our proposed phased array system can increase the capacity margin of next-generation MIMO-enabled IoT communications.