A Novel Reversal Γ-Shape Coupled Inductor High-Step AC-AC Converter

Abstract

This paper presents a novel reversal Γ-shape coupled inductor high-step AC-AC converter. This converter uses a reversal Γ-shape coupled inductor that consists of a two-winding coupled inductor for higher voltage gain. As the coupling inductance ratio is closer to 1 or the duty ratio is larger, the boosting capability of this converter is enhanced. The proposed converter has the following advantages: first, it can realize a continuous input current. Second, the input and output voltage have a common ground in the proposed converter. Apart from these features, the proposed topology has a higher voltage gain with a lower voltage stress on switches and the proposed topology has low cost, and a simple configuration and control scheme. The gain of the proposed high-step AC-AC converter is determined by more variables. Thus, when designing the converter there are more options to meet different requirements. The principle of operation is described and discussed in this paper. In addition, the operating performance is illustrated and estimated based on simulation and experimental results.

1. Introduction

In recent years, high-voltage AC-AC boost converters are attracting more and more attention. In AC power conversion systems, direct PWM AC-AC converters [1,2], indirect AC-AC converters [3] and matrix converters based on switching device [4] have been widely used. The back-to-back dc-link converters have the disadvantages of the power system pollution caused by the diode-rectifier. The disadvantage of matrix converters is their lower voltage ratio. The two converters mentioned above also have complex structures and commutation strategies. Direct PWM AC-AC converters have merits such as single-stage conversion, simpler topology, easier control, higher efficiency, smaller size, lower cost and lower in-line current harmonics.

Since the end of the last century, more and more DC-DC converters were proposed based on various impedance network layouts [5,6]. In theory, a direct PWM AC-AC converter could be obtained from a DC-DC topology by replacing all unidirectional devices with bidirectional switches [7]. The converters based on impedance have some advantages as increasing the voltage gain, adding more flexible options in the design and a larger adjustment range in the gain adjustment. Traditional single-phase Z-source AC-AC uses a consistent style converters can provide a larger range of output voltage in buck–boost mode, by reversing or maintaining the phase angle [8,9]. However, the main drawback of conventional voltage-fed ZSACs [10] is that the ground in the input and output voltages is not shared. Hence, the feature that the output voltage reverses or maintains its phase angle with the input voltage is not supported well. The authors in [11,12] used direct PWM AC-AC converters to overcome voltage sags and swells as static VAR compensators in power systems. The performance of AC-AC converters can be improved significantly using safe-commutation strategy in switching with PWM control as presented in [13]. A class of single phase PWM AC-AC power converters with simple topologies have been presented in [14]. These include buck, boost, buck–boost, and Cuk converters. Z-source converters applied to DC-AC inverters and ac–ac converters have recently been proposed in [8] and [15,16,17,18]. Trans Z-source inverters have recently been proposed to improve the voltage gain using coupled inductors [18,19]. A quasi-Z-source converter has been presented in [17,20]. The proposed converter utilizes two winding coupled inductors or a two-winding transformer. The main merits of the Γ-source converter can be summarized as continuous input current, common ground, simple configuration and control scheme, realizing higher voltage gains with a lower voltage stress on switches, having more adjustments when changing its gain and having more design options to meet its performance requirements.

The designed novel reversal Γ-shape coupled inductor high-step converter based on the Γ-source impedance network. The Γ-source converter in this paper is showing in Figure 1 below. As we can see from Figure 1, the proposed converter consists of a coupled inductor (L_M), inductor (L), switches (S₁, S₂, S₃, S₄, S₅ and S₆), capacitors (C₁, C_c and C_o) and load (R). The numbers of turns of the two windings of this coupled inductor are N₁ and N₂. The unique characteristic of this converter is that the closer the turns ratio (N = N₁:N₂) of the two windings (N₁ and N₂) is to 1, the more the boosting capability of this converter is enhanced. Therefore, this converter still has better boosting capability at a lower design cost and high engineering application value. To improve the voltage gain and decrease the voltage stress on switches, a capacitor clamping unit has been used in the proposed converter.

2. Study of the Proposed Reversal Γ-Source Ac-Ac Converter

2.1. Circuit Analysis

In this section, the topology proposed in Figure 1 will be analyzed in details. The equivalent circuit of the presented converter is shown in Figure 2. It is clearly seen that the coupled inductor is modeled as a magnetizing inductance $L_M$, a leakage inductance $L_K$, and an ideal transformer. For easier analysis of the circuit, we make some assumptions as follows:

(1)

Assuming that the capacitors ($C_1$, $C_c$ and $C_{\mathrm{o}}$) values are large enough, the voltage across them is fixed over a period.

(2)

All power devices in the experiment were ideal devices.

(3)

Define $L_M/(L_M+L_K)$ as the coupling coefficient K of the coupled inductor and define $N_1/N_2$ as the turn ratio $N$ of the coupled inductor.

Using these definitions, the proposed converter in shoot through and non-shoot through states were shown in Figure 3. Time in the state of Figure 3a in one cycle is written as DT and the time in the state of Figure 3b in one cycle is written as (1-D)T, in which D is the duty cycle and T is the cycle time.

In shoot-through state as shown in Figure 3a, the time interval in this state is DT. Accordingly, the state equations can be derived as:

$$\{\begin{array}{c}{V}_{\mathrm{o}}+V_L-V_{C_2}=0\\ V_{C_C}+V_{L_M}+V_{C_1}-V_{in}=0\\ V_{in}-\frac{N_1+N_2}{N_1}{L}_{L_M}=0\\ I_{C_{\mathrm{o}}}-I_L+\frac{V_{\mathrm{o}}}{R}=0\\ I_{C_c}-I_L+I_{C_1}=0\\ I_{C_1}+\frac{N_1-N_2}{N_2}{I}_{L_M}=0\end{array}$$

(1)

In the non-through state as shown in Figure 3b, the time interval in this state is (1-D)T. Accordingly, the state equations can be derived as:

$$\{\begin{array}{c}{V}_{C_C}+\frac{N_1+N_2}{N_1}{V}_{L_M}-V_{in}=0\\ V_{in}-V_{L_M}-V_{C_1}-V_L-V_{\mathrm{o}}=0\\ I_{C_{\mathrm{o}}}-I_L+\frac{V_{\mathrm{o}}}{R}=0\\ I_{C_1}+\frac{N_1-N_2}{N_2}{I}_{L_M}=0\\ I_{C_C}+\frac{N_1}{N_2}{I}_{L_M}=0\end{array}$$

(2)

In the above formula, V_o is the output voltage, $I_L{}_{{}_M}$ is the current flowing through the inductor $L_M$, $I_{C_{\mathrm{o}}}$ is the current flowing through capacitor $C_{\mathrm{o}}$, $I_C{}_{{}_1}$ is the current flowing through capacitor $C_1$, $I_{\mathrm{C}}{}_{{}_c}$ is the current flowing through capacitor $C_c$, $V_L{}_{{}_M}$ is the voltage across inductor $L_M$, $V_{C_1}$ is the voltage across the capacitor $C_1$, $V_{C_c}$ is the voltage across the capacitor $C_c$.

In one cycle, the average equation is as follows:

$${\displaystyle {\int }_0^{DT}{V}_{L_M}dt}+{\displaystyle {\int }_{DT}^{T_{}}{V}_{L_M}}dt=0$$

(3)

Finally, based on (1)–(3), the voltage gain of the proposed reversal Γ-shape coupled inductor AC-AC converter can be computed as:

$$M=\frac{ND-2N+DK}{(1-D)(K-N)}$$

(4)

In the above formula, M is the voltage gain.

Figure 4 shows the relationship between voltage gain and duty cycle at different coupling coefficients.

It can be obtained from Equation (4) that as the coupling coefficient K increases, the voltage gain of the proposed converter increases. If the coupling coefficient K is infinitely close to 1, the equation can be written as follows:

$$M=\frac{ND-2N+D}{(1-D)(1-N)}$$

(5)

Figure 5 reflects the effect of the turn ratio N on the proposed converter gain. It can be derived from Equations (4) and (5) that the voltage gain would increase while the turns ratio is close to 1. This converter reduces the manufacturing cost while increasing the voltage gain. It also can simplify the structural design.

2.2. Commutation Study of the Proposed Converter

As shown in Figure 2, to implement a bidirectional switch, the two MOSFETs are linked with a common emitter, using a safety commutation strategy to prevent the damage of current and voltage spikes on switches.

The operation states in “in-phase boost mode” when V_in > 0 is shown in Figure 6. Switches S₂, S₄ and S₆ are completely turned ON, while S₁, S₂ and S₃ are switched complementary in high frequency with a small dead time between them.

In non-shoot through state, as shown in Figure 6a, the switch S₁ and S₅ are turned off. The energy of the inductor N₂ stares to transmit to the clamped capacitor C_c. The input source V_in, inductor N₁, and capacitor C₁ are connected in series to provide the energy to load and capacitor C_o. And the magnitude of the inductor L current would increase during this state.

In shoot-through state, as shown in Figure 6b, switches S₁ and S₅ are turned ON. The voltage source V_in charges the input inductor L_M, thus the magnitude of the L_M current would increase gradually. The secondary inductor N₂ and capacitor C_c are connected in series to charge the capacitor C₁. During this mode the energy of the load R is supplied by the output capacitor C_o and inductor L.

When the V_in < 0, the analysis method is like that V_in > 0. And operation states of the converter when V_in < 0 are shown in Figure 7. During this period the switches S₁, S₃ and S₅ are turned ON, while S₂, S₄ and S₆ are switched complementary in high frequency. The gate voltage signals of switches are shown in Figure 8.

2.3. Parameter Design

The coupled inductor parameters of the novel reversal Γ-shape coupled inductor converter has been calculated as follows. In the state of Figure 3b, the voltage of the coupled inductor $L_M$ could be calculated as $\frac{KN}{N+K}{V}_{in}$:

$$u_{L_M}=L_M\frac{di}{dt}$$

(6)

According to the voltage equation of inductor (6), the following equation can be derived:

$$L_M\ge \frac{u_{L_M}dt}{di}$$

(7)

As we can see from the Figure 9, the following equation can be obtained:

$$u_{L_M}=\frac{N_1}{N_1+N_2}{V}_{in}$$

(8)

Thus, Equation (9) can be derived:

$$L_M\ge \frac{\frac{N_1}{N_1+N_2}|V_{in}|dt}{di}$$

(9)

Replacing $di$ with $\Delta i_{L_M}$, we can replace $dt$ with $DT$, so, the following equation can be obtained:

$$L_M\ge \frac{N}{N+1}\frac{DT\left|V_{in}\right|}{\mathsf{\Delta }{i}_{L_M}}$$

(10)

Considering the range of current ripple is $\mathsf{\Delta }{i}_m\le x\%I_{L_M}$, Equation (11) can be derived:

$$L_M\ge \frac{N}{N+1}\frac{DT\left|V_{in}\right|}{x\%I_{L_M}}$$

(11)

Similar to the above deduction process, we could determine the parameters of the capacitor $C_c$. The results can be obtained as:

$$C_c=\frac{DT\left|i_{L_M}\right|}{\mathsf{\Delta }{V}_{C_C}}$$

(12)

Assume that the voltage ripple coefficient of the capacitor is $m\%$, the equation of the value range of the capacitor parameters can be described as:

$$C_c\ge \frac{DT\left|i_{L_M}\right|}{m\%V_{C_C}}$$

(13)

By the same method, the equation of $C_1$ can be written as:

$$C_1\ge \frac{N-1}{N}\frac{DT\left|i_{L_M}\right|}{m\%V_{C_1}}$$

(14)

Finally, the parameter design of the output filter is as follows. The parameter of the output filter inductor is calculated as follows [21]:

$$L=\frac{\epsilon R}{2\pi f_c}$$

(15)

and, the expression of $\epsilon$ is as follows:

$$\epsilon =\frac{1}{R}\sqrt{\frac{L}{C}}$$

(16)

Moreover, the parameter of the output filter capacitor could be derived as:

$$C_{\mathrm{o}}=\frac{1}{2\pi f_c\epsilon R}$$

(17)

$f_c$ represents the cutoff frequency of the output filter. $R$ represents the load resistance. And L represents filter inductor. $\epsilon$ is greater than 0.5 and less than 0.8. The $\epsilon$ is select as 0.6. The efficiency of the filter will reduce when $\epsilon$ is too large or too small:

$$V_{S_1}=V_{C_c}=\frac{(2ND-N-1)}{ND+D-N-1}{V}_{in}$$

(18)

$$V_{S_3}=\frac{(N-1)}{(N+1)(1-D)}{V}_{in}$$

(19)

According to the above equations, we can obtain the voltage of capacitor C₁ and C_c as follows:

$$V_{C_1}=\frac{2D-N-1}{DN-D-N+1}{V}_{in}$$

(20)

$$V_{C_C}=\frac{2ND-N-1}{DN+D-N-1}{V}_{in}$$

(21)

2.4. Proposed Converter Versus Other

Besides the proposed converters based on reversal Γ-shape coupled inductor, there are many converters that have been proposed in previous papers. Detailed related introductions can be found in the respective references.

From

Table 1. Governing equations of the existing converters and the proposed converter.

Topology	Voltage Gain	Maximum Voltage Stress of Switches
Converter in [22]	$\frac{D}{1-D}$	$\frac{\sqrt{2}{V}_{in}}{1-D}$
Converter in [23]	$\frac{1-N+D}{(1-D)}$	$\frac{\sqrt{2}(9D^2+1)V_{in}}{2D(1+D)}$
The proposed converter	$\frac{ND-2N+D}{(1-D)(1-N)}$	$V_{S_{1,2}}=\frac{(2ND-N-1)}{ND+D-N-1}{V}_{in}$ $V_{S_{3,4}}=\frac{(N-1)}{(N+1)(1-D)}{V}_{in}$ $V_{S_{5,6}}=\frac{(\sqrt{2}-D)}{ND+D-N-1}{V}_{in}$

, it could be known clearly that the voltage stresses of switches in the proposed converter are far lower than output voltages, therefore low-voltage-rated power switches can be used in the proposed converter. Apart from this, as we can see from Table 1, in the proposed Γ-shape coupled inductor converters, when the turns ratio comes close to 1, the gain become larger.

When the coupled inductor turns ratio is 1.5, the graphs of Figure 10 and Figure 11 are obtained. Figure 10 and Figure 11 show the output voltage gains and voltage stress of MOSFETs. Figure 10 and Figure 11 show that the voltage gain of proposed reversal Γ-shape coupled inductor converter is higher than that of previous topologies in [22,23] while the voltage stresses are lower. Figure 10 shows that the proposed reversal Γ-shape coupled inductor converter has a higher voltage gain than the converters in [22,23] under the same circumstances. Figure 11 shows that the proposed reversal Γ-shape coupled inductor converter has lower voltage stress than the converters in [22,23] under the same circumstances.

3. Experimental Verifications

To verify the performances of the proposed reversal Γ-shape coupled inductor converter, experiments were carried out according to the experimental parameters given in

Table 2. Experimental parameters.

Components	Parameters	Components	Parameters
Maximum output power P	250 W	Inductor L2	20 $\mathsf{\mu }\mathrm{H}$
Input voltage Vin	30 V	Inductor L	1 mH
Output voltage Vo	250 V	C1 (Capacitor)	4.7 $\mathsf{\mu }\mathrm{F}$
Switching frequency fs	20 kHz	Cc (Capacitor)	4.7 $\mathsf{\mu }\mathrm{F}$
Turns ratio n2/n1 of coupled inductor N	1.5	Co (Capacitor)	20 $\mathsf{\mu }\mathrm{F}$
Inductor L1	45 $\mathsf{\mu }\mathrm{H}$	Power MOSFET Q	IRFP 250 N

. Experimental verification of the proposed novel topology is achieved and controlled using a digital signal processor (TMS320F28335). Switching frequency is set at 20 kHz. The duty cycle is 0.72. The tested condition and experimental parameters are shown in Table 2.

The experimental results of the novel reversal Γ-shape coupled inductor converter have been illustrated in Figure 12. Figure 12a shows the input and output voltages of the proposed reversal Γ-shape coupled inductor converter. In Figure 12a, the green waveform is the input voltage waveform and the yellow waveform is the output voltage waveform.

As we can see from the result, the input voltage amplitude of the proposed converter is 30 V and the output voltage amplitude of the proposed converter is about 250 V. Both the input and output voltages are sinusoidal. The voltage gain of the proposed converter was verified. The input current has been shown in Figure 12b which is also a sinusoidal waveform. Figure 12c shows the voltage stress of the switch S₁. As can be seen from Figure 12c, the maximum voltage stress on switch S₁ is about 13 V. The experimental results agree with the calculation, which verifies the validity of our theoretical analysis.

4. Conclusions

In this article, a novel reversal Γ-shape coupled inductor high-step AC-AC converter is presented. The proposed converter utilizes a safe commutation strategy to avoid voltage and current spikes. The modulation strategy, analysis of operation states and parameter design are introduced. The input voltage and output voltage share the same ground, which is beneficial for reducing the input current harmonics. As the coupling inductance ratio is closer to 1 or the duty ratio is larger, the voltage gain of this converter is enhanced. This exclusive feature is beneficial to reduce the structural cost of the converter while achieving high voltage gain. The gain of the proposed high-step AC-AC converter is determined by more variables. Thus, when designing the converter there are more options to meet different requirements. Finally, the experimental results prove the correctness of the theoretical analysis. The proposed converter has better performance that other proposed devices.