A Traction Three-Phase to Single-Phase Cascade Converter Substation in an Advanced Traction Power Supply System

Abstract

The advanced traction power supply system (ATPSS) is a new directional development for traction power supply systems, which can totally remove the neutral sections and effectively promote power quality. However, the existing converters suffer from small substation capacity. In this paper, a new configuration based on a three-level neutral point clamped (3L-NPC) three-phase to single-phase cascade converter in a substation is proposed for ATPSS, which can be used to match the capacity of the converter for high voltage and large power applications. The control strategy of the proposed converter is analyzed in depth, and the phase disposition sinusoidal pulse width modulation (PD-SPWM) with phase shift carrier SPWM (PSC-SPWM) is employed in the inverters. Then, the inductance equalizing circuit is applied for the voltage balance on the DC-link. Besides, a LC filter circuit is designed to eliminate the double line-frequency ripple of DC voltage. Afterwards, a simulation model and an experimental prototype are developed, respectively. The simulation results show that the proposed converter in this paper can not only meet the requirements of voltage and capacity for the traction network, but also improve power quality. Finally, the experimental results verify the correctness and feasibility of the proposed control strategy.

1. Introduction

As a focus of public opinion in 2015, the “One Belt, One Road” project has attracted the eyes of the world, in which a fast and comfortable high-speed railway would connect the East with the West [1,2]. The traction power supply plays one of the most important roles in a high-speed railway. The existing two-phase traction power supply in China is shown in Figure 1a. In the traction substation, the voltage of the three-phase grid is transformed into two-phase voltage by a transformer [3]. Due to the differences of phase, amplitude and frequency of the voltage between the adjacent arms α1 and β1 (α2 and β2), neutral sections must be set between the adjacent arms [4]. There are mainly three problems caused by neutral sections: power quality issues such as unbalance, reactive power and low-order harmonics; disturbance between locomotive and network; speed loss of the locomotive. With the rapid development of high-speed railways, how to solve the aforementioned problems is a pressing problem.

The co-phase traction power supply system developed by Chinese scholars is analyzed in depth in [5], which has been put into trial operation in Meishan, China. The structure of co-phase traction power supply is shown in Figure 1b, where the neutral sections NS1 and NS3 could be canceled. The system solves the problems of power quality for electric railway with power electronic compensation devices—Active Power Compensators (APCs). Furthermore, the number of neutral sections is halved [6].

In [7], the advanced traction power supply system (ATPSS) based on a three-phase to single-phase converter is proposed, of which the system structure is shown in Figure 1c. There is a step-down transformer on the input side and a step-up transformer on the output side in a traction substation, respectively. The system achieves a balanced three-phase grid load and controls the output of the traction network flexibly by using power electronics. Besides, the system could improve power quality and cancel the neutral sections totally, which is a new type of traction power supply system and a new exploration avenue in the related research. However, the output current is significantly uplifted in the light of step-down transformer ratio, which calls for more equipment requirements. In addition, due to the current restriction on the development of power electronic devices, the traditional two-level or tri-level or five-level structure couldn’t meet the requirements of the traction power supply system capacity. Nowadays, the research mainly focuses on how to enhance the system capacity. A multi-level cascade converter has the advantages of larger capacity and simpler control technique [8,9,10], therefore, multi-level cascade converters can be applied to this system.

Consequently, in practical applications clamped multi-level converters mainly consist of three-level and five-level converters. Theoretically, any level of the output voltage could be obtained by cascading multiple converter modules. The output transformer in a traction substation of ATPSS can be canceled to enlarge the system capacity by means of cascading multilevel converters if the interface voltage level were higher than the output voltage level [11,12]. At the same time, if the number of cascade modules or the levels of multi-converter module were too large, it will cause difficulties in the design of the control system. It is important to work out a proper cascade system, especially for an engineering application of high reliability requirements [13]. Along with the improvement of power electrical device, the new IGBTs (Insulated Gate Bipolar Transistor) make it possible that high-voltage and large-power applications come true, such as SiC and other devices described in [14,15].

Figure 1. Traction power supply system modes: (a) The existing traction power supply system; (b) The co-phase traction power supply system; (c) The advanced traction power supply system.

Figure 1. Traction power supply system modes: (a) The existing traction power supply system; (b) The co-phase traction power supply system; (c) The advanced traction power supply system.

According to the analysis above, a new traction substation based on a three-phase to single-phase cascade converter in ATPSS is proposed in this paper. The system inherits the advantages of the original traction substation in ATPSS. In this way, problems caused by the output transformer are solved and the interface voltage of the converter is improved to meet the requirements of traction substation capacity.

The paper is organized as follows: Section 2 is dedicated to introducing the proposed three-level neutral point clamped (3L-NPC) cascade converter in a traction substation, and the 3L-NPC three-phase to single-phase is analyzed in detail. The simulation and experimental results are discussed in Section 3. The conclusions are presented in the last part.

2. Configuration

The proposed 3L-NPC cascade converter based on a three-phase to single-phase in a traction substation is shown in Figure 2. The substation consists of a multi-windings step-down transformer connecting to the three-phase grid and several three-phase to single-phase AC-DC-AC converters, which are cascaded in the output terminal. The output of the system is an AC voltage satisfying the load requirements. The traction networks of the adjacent substations connect with each other to form the ATPSS. Meanwhile, the transformers provide isolated input voltages between different converters. Then the outputs of different converters can be connected in series and combined to generated one high voltage traction supply.

Figure 2. The diagram of proposed traction substation system in advanced traction power supply system (ATPSS).

Figure 2. The diagram of proposed traction substation system in advanced traction power supply system (ATPSS).

Owing to the limitations of the present level of power electronic devices, the cascade modules could output several times the voltage of a single module. The 3L-NPC three-phase to single phase converter configuration is shown in Figure 3, taking the traction network capacity and the complexity of control strategy into consideration. The converter is made up of a three-phase 3L-NPC rectifier, auxiliary DC equalizing circuit, LC filter circuit, and single-phase 3L-NPC inverter. The three-phase and single-phase PWM converter can operate in four-quadrant mode, which is able to transfer energy on both sides of a three-phase to single-phase system. It’s realized that the system achieves active balanced current of the power grid using the three-phase PWM rectifier system. At the same time, the system provides network capacity in the same phase using a single-phase PWM inverter.

Figure 3. Three-level neutral point clamped (3L-NPC) three-phase to single phase converter with equalizing circuit.

Figure 3. Three-level neutral point clamped (3L-NPC) three-phase to single phase converter with equalizing circuit.

2.1. Control of Three-Phase Rectifier

The three-phase PWM rectifier operates under rectifier mode and active inversion mode in the four-quadrant with the traditional PWM rectifier control strategy [16]. The system controls the active and reactive components of the input signals in the dq coordinate. Both the active current exchange between AC side and DC side and the stabilization control of DC voltage can be achieved. Specifically, a stable DC voltage is achieved by controlling the magnitude and direction of the active current between three-phase grid and the DC capacitor. The detail control principle is shown in Figure 4.

Figure 4. Block control diagram of the three-phase PWM rectifier.

Figure 4. Block control diagram of the three-phase PWM rectifier.

The grid current signal i_abc is transformed into i_d and i_q by the abc-dq transformation and the phase information of voltage v_abc, which is acquired with a phase locked loop (PLL). Therefore, active and reactive power decoupling can be achieved. Then the DC voltage v_dc is compared with a given reference voltage v_dcref. The error of v_dc and v_dcref will go through PI (proportional integral) controller and then compared with the d component of the three-phase current, then the result will go through another PI controller as an output current. In the meanwhile, the q component of the three-phase current is compared to a given value 0, and the PI controller output a value, which controls the q component of the command signal. Then the dq components of the voltage are obtained using the mathematical relationship between the current and voltage after the inverse transformation. Afterwards, the switch control signals will be accomplished with a space vector PWM (SVPWM) control module. By the operation above, the stability of the DC voltage can be achieved. Furthermore, it’s able to ensure that rectifier is operating under the unity power factor and the impact on power quality of the public traction network will be reduced.

2.2. Control of Single-Phase Cascade Inverter

Assuming that the traction network is working properly, ATPSS requires the cascade converter could actively connect to the traction network and maintain the stability of the port voltage amplitude and frequency in the traction network. Besides, the converter can provide active and reactive current depending on the load requirements and satisfy the need that multiple substations can be automatically assigned current according to the load and the impedance of the traction network. Therefore, the single-phase PWM inverter output voltage can be equivalent to a voltage source, whose frequency, phase and amplitude are adjustable.

The number of inverter cells N depends on the desired output voltage level, which is synthesized by adding up all the H-bridge cells output voltage as v_o = v_o1 + v_o2 + v_o3 + … + v_oN. In a cascade system that utilizes equal sets of DC sources (V_dc1 = V_dc2 = V_dc3 = … = V_dcN), the number of output voltage levels is N × (m−1) + 1, where N is the number of cascade cells and m is the number of output voltage levels in each multilevel H-bridge cells, here m = 5.

It is necessary to get a controllable amplitude, frequency and phase voltage source model in the ATPSS. In this paper, the outer voltage could make a stable modulation. The control principle is shown in Figure 5. v_tr, that is referred as traction network detected actual voltage, is compared with v_trref recognized as a given reference voltage. The result passes the PI controller and its output operates as a co-modulated wave (u_m) of each 3L-NPC three-phase to single-phase converter module. Carrier (u_cN) is calculated by phase carrier shift SPWM (PSC-SPWM) technique. Inverter modulation method used in the 3L-NPC three-phase to single-phase converter module is phase disposition SPWM (PD-SPWM) [17].

Figure 5. Block control diagram of the single-phase PWM (pulse width modulation) cascade inverter.

Figure 5. Block control diagram of the single-phase PWM (pulse width modulation) cascade inverter.

The schematic of PSC-SPWM used in cascade inverters is shown in Figure 6. The Fourier fundamental of the output voltage of an H-bridge is:

$$\frac{v_{\text{o}}}{v_{\text{dc}}}=Nm\sin \text{ω}t+{\displaystyle \sum _{n=1}^{\infty }\frac{4}{n\pi }}\cos (\frac{n\pi }{2}){\displaystyle \sum _{k=1}^{\infty }{J}_k\frac{mn\pi }{2}}\cdot [A\sin (k\pm n{k}_{\text{c}})\text{ω}t+2B\sin (k\text{ω}t)\sin (n{\text{ω}}_{\text{c}}t)]$$

(1)

In Equation (1), J_k is on behalf of the k-th Bessel function and v_dc is the DC voltage. Besides, v_o represents the output voltage of the inverter.

Figure 6. Phase shift carrier schematic.

Figure 6. Phase shift carrier schematic.

$$\{\begin{array}{c}A=\cos n{\text{θ}}_1+\cos n{\text{θ}}_2+\dots +\cos n{\text{θ}}_N\\ B=\sin n{\text{θ}}_1+\sin n{\text{θ}}_2+\dots +\sin n{\text{θ}}_N\end{array}$$

(2)

In Equation (2), θ_k (k = 1, 2, 3…N) is phase shift angle. The increasing angle of each H-bridge is θ_k = π/N (N is the number of H-bridge):

$$\{\begin{array}{c}A=\cos (n\cdot 0\cdot \frac{\pi }{N})+\cos (n\cdot 1\cdot \frac{\pi }{N})+\dots +\cos [n(N-1)\frac{\pi }{N}]\\ B=\sin (n\cdot 0\cdot \frac{\pi }{N})+\sin (n\cdot 1\cdot \frac{\pi }{N})+\dots +\sin [n(N-1)\frac{\pi }{N}]\end{array}$$

(3)

In Equation (3), there is n = 2, 4, 6 …, B = 0 and when n < 2N, the A = 0 is established. As can be seen from the above derivation, the total output voltage of the H-bridge is the algebraic sum of the basic units. Cascade inverters can be equivalent to a high single carrier frequency converter. The equivalent frequency is 2N times as the frequency of the carrier. In conclusion, PSC-SPWM can be implemented equivalent to the function of higher switching frequency with low power switching devices so that the switching loss can be reduced.

2.3. DC-Link for the Three-Phase to Single-Phase Converter

When the multilevel diode clamped converter transfers active power, the DC capacitor voltage will become unbalanced. To solve the problem of DC capacitor voltage unbalance, an inductive auxiliary circuit is added to this paper on the DC-link [18].

The diagram of the inductance equalizing circuit is shown in Figure 7. The specific control principle is as follows: when V_c1 is larger than V_c2, SA1 turns on while SA2 is off, then the capacitor C1 will be discharged with the inductance LA. The capacitor’s voltage V_c1 decreases, and the inductance’s current increases. Since the energy stored in C1 is delivered to LA via the path shown in Figure 7a, the voltage V_c1 decreases and V_c2 remains unchanged. Meanwhile, the discharge current i_LA1 will increase linearly from zero. Secondly, SA1 is turned off, and SA2 also maintains an off state. The anti-parallel diode DA2 provides a discharge path for LA as shown in Figure 7b. The energy stored in LA will be delivered to C2. Therefore V_c2 increases, whereas V_c1 remains unchanged. This stage will be ended once i_LA1 reaches zero. The process will not end up until V_c1 = V_c2. On the contrary, if V_c1 < V_c2, the process is just the opposite.

Figure 7. The inductance equalizing circuit of 3L-NPC. (a) Discharge current path from C1 to LA at V_C1 > V_C2 stage 1; (b) Charge current path from LA to C2 at V_C1 > V_C2 stage 2.

Figure 7. The inductance equalizing circuit of 3L-NPC. (a) Discharge current path from C1 to LA at V_C1 > V_C2 stage 1; (b) Charge current path from LA to C2 at V_C1 > V_C2 stage 2.

As is well known, a double line-frequency ripple of DC voltage would appear on the DC-link [19]. In this paper, a LC filter circuit is designed to eliminate the double line-frequency ripple:

$$i_{\text{dc2}}=-\frac{V_{\text{t}}{I}_{\text{t}}}{N{V}_{\text{dc}}}\cos (2{\text{ω}}_{0}t-\text{φ})$$

(4)

where, i_dc2 is the twice grid-frequency current, V_t and I_t are the voltage and current of cascade inverter output, respectively. V_dc is the DC-link voltage of each three-phase to single-phase converter, ω₀ is angular frequency, φ is the power factor angle of the load. When the circuit is under resonant state, i_dc2 flow through the LC filter circuit. Therefore, the capacitor’s voltage v_c of the LC filter is shown in Equation (5):

$$v_{\text{C}}=-\frac{V_{\text{t}}{I}_{\text{t}}}{2C{\omega }_{0}N{V}_{\text{dc}}}\sin (2{\omega }_{0}t-\text{φ})$$

(5)

Generally, the amplitude of v_c is less than 10% of DC-link voltage. So the L (inductor) and C (capacitor) is designed in Equations (6) and (7):

$$C\ge \frac{5V_{\text{t}}{I}_{\text{t}}}{{\omega }_{0}N{V}_{\text{dc}}^2}$$

(6)

$$L=\frac{1}{4C{{\omega }_0}^2}$$

(7)

3. Simulation and Experiment Results

3.1. Simulation and Analysis

In order to verify the system’s control strategy proposed above, a 3L-NPC three-phase to single-phase cascade converter for a substation shown in Figure 2 is used to conduct a simulation by MATLAB/SIMULINK (MathWorks, Natick, MA, USA) in this paper. The main simulation parameters are listed in Table 1.

Table 1. System and control parameters.

Parameters	Values
Three-phase power source voltage	110 kV
Rated frequency	50 Hz
The standard of multi-windings transformer	110 kV/3.5 kV
The standard of IGBT	6.5 kV
Cells	8
DC-link voltage	7 kV
DC-link capacitance	3 mF
The inductance of three-phase input side	3 mH
The inductance of single-phase output side	2 mH
The reference voltage of traction network	27.5 kV
The inductance of auxiliary circuit	1 mH
The filter circuit	3 mF/0.84 mH
Load	100 Ω
Switching frequency of carrier	6 kHz

Table 1. System and control parameters.

Parameters	Values
Three-phase power source voltage	110 kV
Rated frequency	50 Hz
The standard of multi-windings transformer	110 kV/3.5 kV
The standard of IGBT	6.5 kV
Cells	8
DC-link voltage	7 kV
DC-link capacitance	3 mF
The inductance of three-phase input side	3 mH
The inductance of single-phase output side	2 mH
The reference voltage of traction network	27.5 kV
The inductance of auxiliary circuit	1 mH
The filter circuit	3 mF/0.84 mH
Load	100 Ω
Switching frequency of carrier	6 kHz

A discrete modeling algorithm is used in the simulation. The sampling time is 1 μs. The influence of double line-frequency ripple in three-phase to single-phase on the DC-link is exhibited in this paper. What’s more, the performance characteristics of no-load and load-supporting is also presented by this simulation. The simulation time is 1.2 s and there is no-load before 0.4 s, while the system is loaded after 0.4 s. During this period time, the LC filter circuit comes into operation after 0.9 s.

The DC voltage v_dc is shown in Figure 8. As can be seen from the figure, the voltage of each capacitor become stable at 3.5 kV after about 0.1 s regulation time at no-load. When the circuit is loaded at 0.4 s, the system responds quickly with restoring homeostasis in 0.2 s. Because of the double line-frequency ripple added into the single-phase inverter DC side, the voltage produces slight fluctuations at 3.5 kV in the steady state, and the amount of pulsation is about 5.7% of the DC voltage. After 0.9 s, the double line-frequency ripple disappears as the LC filter circuit going up. Besides, the results verified that the voltage equalization could be achieved by the inductance equalizing circuit.

Figure 8. The DC voltage of three-phase to single-phase converter.

Figure 8. The DC voltage of three-phase to single-phase converter.

The currents i_sabc of the three-phase to single-phase converter in the grid are displayed in Figure 9. The currents change a lot during the simulation process. Before 0.2 s, the three-phase power charges the DC capacitances. Because the system is at no-load in 0–0.4 s, the output currents are substantially zero before the DC voltage charging is completed. When the load is added at 0.4 s, the currents increase quickly. The waveforms become irregular with a large number of injected harmonics, owing to the double line-frequency ripple appearing on the DC-link of the three-phase to single-phase converter. The LC filter circuit is put into operation after 0.9 s and the double line-frequency ripple is eliminated rapidly. During 1.16–1.20 s, the currents exhibit a good sinusoidal waveform and the current distortion disappears from the LC filter circuit. What’s more, the Total Harmonic Distortion (THD) of the three-phase currents i_sabc is 2.46% in the steady situation. Figure 10 shows that the voltage is in phase with the current of phase A. The results verify that the converter designed in this paper can run at unity power factor. In addition, a good dynamic response was found during system startup. The three-phase to single-phase converter is equivalent as well as a resistive load for three-phase grid.

The output voltage of the cascade converters, namely traction network voltage waveform v_tr, is illustrated in Figure 11. The voltage waveform is a multi-level staircase under no-load. The output voltage nearly becomes a sinusoidal waveform after 0.4 s since the inductance filter circuits are used in inverters.

Figure 9. The currents in the grid.

Figure 9. The currents in the grid.

Figure 10. The voltage and current of phase A in the grid.

Figure 10. The voltage and current of phase A in the grid.

Figure 11. The voltage of traction network.

Figure 11. The voltage of traction network.

With the rising output cascade levels, the switching frequency decreases. Therefore, the loss of switching also comes down. As is shown in Figure 12, the THD of the voltage of traction network is 0.31%, which illustrates that the cascade system could reduce the harmonics and promote power quality. Meanwhile, the cascade system has low requirements for filter circuit design, when the cascade number is high enough, the harmonic content is very low. Then it is possible to cancel the filter circuit to save on circuit costs.

Figure 12. The Total Harmonic Distortion (THD) of voltage of the traction network.

Figure 12. The Total Harmonic Distortion (THD) of voltage of the traction network.

3.2. Experiments and Analysis

In order to verify the performance of the cascade system proposed, an experimental setup of a 3L-NPC three-phase to single-phase cascade converter has been developed. Figure 13 is a photo of the prototype. The major experimental parameters is listed in Table 2. All the control algorithms and assistant modules are implemented by Verilog-HDL (Hardware Description Language), one of universal IEEE industry standard hardware description languages used to describe digital systems and design hardware realization in code method.

In Figure 14a, the phase A voltage v_sa and current i_sa of transformer on the primary side are illustrated, and both the voltage and current are in the same phase, so the rectifier is working within unity-power factor limits. For the three-phase grid, the cascade system is a pure resistive load. The current i_sa on the primary side is added up by the A phase current i_a1 and i_a2 in the secondary side, which is displayed with Ch2 and Ch4. Figure 14b presents the DC voltage, the voltage and current of load without the LC filter circuit, while Figure 14c shows the same variables within the LC filter circuit. An obvious double line-frequency ripple of DC voltage appears without LC filter circuit, while it disappears within LC filter circuit, which proves the analysis above. The ripple has a bad influence on the inverter output, producing a slight shift on the output voltage. When the LC filter circuit begins to work, the shift disappears. It is confirmed that LC filter circuit is effective for the ripple. Figure 14d shows the voltage of output and load, v_otr and v_tr. The true root mean square value voltage of load is controlled to the given value 100 V. The waveform is very smooth and verifies the control strategy of the converter. A high quality voltage could be obtained from the proposed converter. Figure 14e exhibits the voltage and current of load when the load step changes. In two fundamental cycles, the voltage and current make a quick adjustment to recover sinusoidal waveforms. It follows that the dynamic characteristics of control system is verified. Figure 14f also demonstrates a satisfactory control performance. The steady-state characteristics and dynamic characteristics of the system are greatly increased.

Figure 13. Photo of the experimental prototype.

Figure 13. Photo of the experimental prototype.

Table 2. Experimental circuit parameters.

Parameters	Values
The voltage on primary and secondary side of transformer	50 V/50 V
Cells	2
Rated frequency	50 Hz
DC-link voltage	100 V
DC-link capacitance	470 µF
The inductance of three-phase input side	2 mH
The inductance of single-phase output side	2 mH
The inductance of auxiliary circuit	1 mH
The filter circuit	2.2 mF/1 mH
Load	100 Ω
Switching frequency of carrier	3 kHz

Table 2. Experimental circuit parameters.

Parameters	Values
The voltage on primary and secondary side of transformer	50 V/50 V
Cells	2
Rated frequency	50 Hz
DC-link voltage	100 V
DC-link capacitance	470 µF
The inductance of three-phase input side	2 mH
The inductance of single-phase output side	2 mH
The inductance of auxiliary circuit	1 mH
The filter circuit	2.2 mF/1 mH
Load	100 Ω
Switching frequency of carrier	3 kHz

Figure 14. Experiment results: (a) The currents of transformer, CH1: the voltage of phase A in the primary side v_sa, CH3: the current of phase A on the primary side i_sa, CH2: the current of phase A on secondary side i_a1, CH4: the current of phase A on secondary side i_a2; (b) The DC voltage without LC filter circuit and voltage and current of load, CH1: DC voltage V_dc1, CH2: DC voltage V_dc2, CH3: output voltage v_o, CH4: the current of load i_load; (c) The DC voltage with LC filter circuit and voltage and current of load, CH1: DC voltage V_dc1, CH2: DC voltage V_dc2, CH3: output voltage v_o, CH4: the current of load i_load; (d) The output voltage and load voltage, CH3: output voltage v_otr, CH4: load voltage v_tr; (e) The voltage and current of load when the load step change, CH1: load voltage v_load, CH3: load current i_load; (f) Dynamic waveforms of voltage when the load step changes, CH3: output voltage v_otr, CH4: load voltage v_tr.

Figure 14. Experiment results: (a) The currents of transformer, CH1: the voltage of phase A in the primary side v_sa, CH3: the current of phase A on the primary side i_sa, CH2: the current of phase A on secondary side i_a1, CH4: the current of phase A on secondary side i_a2; (b) The DC voltage without LC filter circuit and voltage and current of load, CH1: DC voltage V_dc1, CH2: DC voltage V_dc2, CH3: output voltage v_o, CH4: the current of load i_load; (c) The DC voltage with LC filter circuit and voltage and current of load, CH1: DC voltage V_dc1, CH2: DC voltage V_dc2, CH3: output voltage v_o, CH4: the current of load i_load; (d) The output voltage and load voltage, CH3: output voltage v_otr, CH4: load voltage v_tr; (e) The voltage and current of load when the load step change, CH1: load voltage v_load, CH3: load current i_load; (f) Dynamic waveforms of voltage when the load step changes, CH3: output voltage v_otr, CH4: load voltage v_tr.

4. Conclusions

A 3L-NPC three-phase to single-phase cascade converter for railway substations is proposed in this paper. The related control strategy of rectifier and cascade inverter are analyzed in detail, respectively. In addition, an inductance equalizing circuit and LC filter on the DC-link are designed. Based on the analysis above, a simulation system is built. The results show that the converter could satisfy the requirements of voltage and capacity for a traction network. The goal of unity power factor with low harmonic content is also met in the three-phase grid. Besides, a good dynamic and static performance is also exhibited in this paper. Moreover, the double line-frequency ripple of converter could be cleared up by the LC filter circuit, reducing the negative impact on the power quality of the traction network. The small-scale experimental results demonstrate the basic function and dynamic performance of the proposed system as well.