A Compact Crossed Inverted-V Antenna with a Common Reﬂector for Polarization Diversity in the IoT

: This article presented a compact and high gain antenna with reconﬁgurable polarization based on two inverted-V dipoles fabricated in a crossed conﬁguration, and with a common planar reﬂector. The proposed antenna could generate four di ﬀ erent types of polarizations, such as vertical polarization (VP), horizontal polarization (HP), right-hand circular polarization (RHCP), and left-hand circular polarization (LHCP). A pair of inverted-V dipoles drove the polarization diversity, where each dipole had an integrated matching circuit and a microstrip balun. Using a crossed inverted-V conﬁguration with a ground plane as the common reﬂector, we could achieve compactness in size, high directivity, and a wider beamwidth than a normal dipole antenna. To verify the performance of the proposed antenna, we fabricated a sub-6GHz antenna with a Taconic TLX-9 substrate, which had a relative permittivity of 2.5. The proposed antenna showed a measured 10-dB impedance bandwidth of 752 MHz (5.376 GHz to 6.128 GHz). The peak gains for the VP, HP, RHCP and LHCP operations at 5.8 GHz were about 5.2 dBi, 4.61 dBi, 5.25 dBic, and 5.51 dBic, respectively. In addition, the half-power beamwidth (HPBW) for all the polarizations were greater than 78 ◦ in the operation band.


Introduction
Since South Korean carriers have officially launched the world's first commercial fifth generation (5G) service, the demand for high speed, low latency, large capacity, and massive connectivity in communication has grown more rapidly [1][2][3].Moreover, given the rise of 5G communication, the demand for extended or new applications has accelerated, are more intensive research is required on the Internet of Things (IoT), specifically on devices that converge with the 5G network.Thus, in order to deploy successful and reliable 5G services, improvements are necessary in the 5G IoT device technologies.Although there is a broad spectrum for advanced research in the 5G IoT, the challenges in antenna technology are a primary concern.Owing to increased device connectivity in the 5G environment, simultaneous multi-device communication is unavoidable and, therefore, high electromagnetic (EM) interferences may cause a significant degradation in the device performances [4][5][6][7].To facilitate multi-device communication with a reliable interference rejection, an antenna or antennas supporting polarization diversity are required.Especially, all types of polarizations, including horizontal polarization (HP), vertical polarization (VP), right-hand circular polarization (RHCP), and left-hand polarization (LHCP) are required to achieve the maximum spectral efficiency [8][9][10][11][12][13][14][15]. Figure 1 shows the conceptual diagram for the 5G IoT devices or sensors possessing a limited polarization and polarization diversity, as proposed in this article.As shown in Figure 1a, if multiple devices carrying various information are connected and simultaneously communicating with other devices, then signal interferences from neighboring devices cannot be avoided.However, if we transmit and receive various information through different polarizations, as shown in Figure 1b, the spectral channels can be isolated, thereby achieving greater immunity to interferences.
Electronics 2019, 8, x FOR PEER REVIEW 2 of 11 devices carrying various information are connected and simultaneously communicating with other devices, then signal interferences from neighboring devices cannot be avoided.However, if we transmit and receive various information through different polarizations, as shown in Figure 1b, the spectral channels can be isolated, thereby achieving greater immunity to interferences.To provide polarization diversity, it is possible to adapt and use multiple antennas with different types of fixed polarizations, although the increase in overall size is not preferable.Since most of the modern antenna technology needs to support array architectures, a single radiation antenna by itself should also be as compact as possible.However, due to the trade-off relationship between the antenna size and radiation gain characteristics, an efficient technique to achieve high directivity whilst keeping the antenna size as compact as possible should be investigated.Additionally, the antenna characteristics at near-6 GHz changes significantly from the same antenna architecture operating below 3 GHz, citing a stronger coupling effect for compact designs.Thus, effective researches are also required on near-6 GHz compact antenna structures for IoT applications.There have been previous researches to realize the antennas with various polarization characteristics [8][9][10][11][12][13][14][15][16][17][18][19].Some of the previous studies showed antennas with dual-or quadri-polarizations [8,9,12,15], but they suffered from low gain, large size, complicated air-bridge implementation, or large gain variation in the different polarization modes.Moreover, some antennas used crossed-dipole structures to drive circular polarizations [13,14,16,17,19].However, the antennas also had drawbacks via the large number of PIN diode switches, only single or dual polarizations, or the requirement for conductingwalls.Other types of researches showed reconfigurable radiation patterns, although multiple polarizations were not supported [20][21][22].In addition, several other researches showed reconfigurable polarizations based on a reconfigurable feed network, but a large number of PIN diode switches, large antenna size, or limited number of polarization types remained unsolved [23][24][25][26][27].Moreover, there are few antennas in a crossed configuration satisfying near-6 GHz realization, compactness in volume, and reconfigurability for all polarization types.Therefore, in this article, we proposed a new compact antenna based on a crossed inverted-V structure, with a ground plane as the common reflector at 5.8 GHz.The proposed structure can generate four different types of polarizations (HP, VP, RHCP, and LHCP), and it can provide high directivities for all polarizations, despite its compact size.That is, for the first time, using the proposed structure, we verified the advanced qualifications, including the compactness in volume, high gain compared to a regular dipole, quad-polarizations, and the practical performance of the crossed structure above 5 GHz.In Section 2, we discuss the analysis for antenna design, including the feed network and matching circuit.Then, in Section 3, we presented the simulated and measured results at the center frequency of 5.8 To provide polarization diversity, it is possible to adapt and use multiple antennas with different types of fixed polarizations, although the increase in overall size is not preferable.Since most of the modern antenna technology needs to support array architectures, a single radiation antenna by itself should also be as compact as possible.However, due to the trade-off relationship between the antenna size and radiation gain characteristics, an efficient technique to achieve high directivity whilst keeping the antenna size as compact as possible should be investigated.Additionally, the antenna characteristics at near-6 GHz changes significantly from the same antenna architecture operating below 3 GHz, citing a stronger coupling effect for compact designs.Thus, effective researches are also required on near-6 GHz compact antenna structures for IoT applications.There have been previous researches to realize the antennas with various polarization characteristics [8][9][10][11][12][13][14][15][16][17][18][19].Some of the previous studies showed antennas with dual-or quadri-polarizations [8,9,12,15], but they suffered from low gain, large size, complicated air-bridge implementation, or large gain variation in the different polarization modes.Moreover, some antennas used crossed-dipole structures to drive circular polarizations [13,14,16,17,19].However, the antennas also had drawbacks via the large number of PIN diode switches, only single or dual polarizations, or the requirement for conducting-walls.Other types of researches showed reconfigurable radiation patterns, although multiple polarizations were not supported [20][21][22].In addition, several other researches showed reconfigurable polarizations based on a reconfigurable feed network, but a large number of PIN diode switches, large antenna size, or limited number of polarization types remained unsolved [23][24][25][26][27].Moreover, there are few antennas in a crossed configuration satisfying near-6 GHz realization, compactness in volume, and reconfigurability for all polarization types.Therefore, in this article, we proposed a new compact antenna based on a crossed inverted-V structure, with a ground plane as the common reflector at 5.8 GHz.The proposed structure can generate four different types of polarizations (HP, VP, RHCP, and LHCP), and it can provide high directivities for all polarizations, despite its compact size.That is, for the first time, using the proposed structure, we verified the advanced qualifications, including the compactness in volume, high gain compared to a regular dipole, quad-polarizations, and the practical performance of the crossed structure above 5 GHz.In Section 2, we discuss the analysis for antenna design, including the feed network and matching circuit.Then, in Section 3, we presented the simulated and measured results at the center frequency of 5.8 GHz to verify the performance of the proposed work at sub-6 GHz IoT applications.Lastly, we drew our conclusion in Section 4.

Antenna Design
Figure 2a shows the proposed antenna with a pair of inverted-V dipoles and a ground plane as the common reflector.Figure 2b shows a single inverted-V dipole and total two inverted-V dipoles, designed in a crossed configuration for the proposed architecture.Figure 2c shows the integrated feed network and the layer information for the proposed architecture.The feed network was based on a microstrip line balun with tuning stubs, which considered a strong coupling due to the tightly crossed configuration.Thus, one inverted-V dipole could generate a HP and the other inverted-V dipole could generate a VP when they were individually excited.In addition, when both the inverted-V dipoles were simultaneously excited with a 90 • phase difference, the RHCP or LHCP could be generated depending on the 90 • phase lead or the lag relationship between the two inverted-V dipoles.Unlike a normal inverted-V configuration, we placed the ground reflector below the crossed inverted-V to make a radiation pattern towards the broadside with a high directivity.
Electronics 2019, 8, x FOR PEER REVIEW 3 of 11 GHz to verify the performance of the proposed work at sub-6 GHz IoT applications.Lastly, we drew our conclusion in Section 4.

Antenna Design
Figure 2a shows the proposed antenna with a pair of inverted-V dipoles and a ground plane as the common reflector.Figure 2b shows a single inverted-V dipole and total two inverted-V dipoles, designed in a crossed configuration for the proposed architecture.Figure 2c shows the integrated feed network and the layer information for the proposed architecture.The feed network was based on a microstrip line balun with tuning stubs, which considered a strong coupling due to the tightly crossed configuration.Thus, one inverted-V dipole could generate a HP and the other inverted-V dipole could generate a VP when they were individually excited.In addition, when both the inverted-V dipoles were simultaneously excited with a 90° phase difference, the RHCP or LHCP could be generated depending on the 90° phase lead or the lag relationship between the two inverted-V dipoles.Unlike a normal inverted-V configuration, we placed the ground reflector below the crossed inverted-V to make a radiation pattern towards the broadside with a high directivity.As shown in Figure 2c, we used a 4-layer feed network including a reflector plane to drive the polarization diversity.We integrated one feed network on the second layer for the VP inverted-V dipole and the other feed network was integrated on the bottom layer (layer-4) for the HP inverted-V dipole.Additionally, the third layer was only inserted for rigidity and implementation purposes.Each feed network consisted of two 100 Ω lines with a phase difference of 180°, and it was matched As shown in Figure 2c, we used a 4-layer feed network including a reflector plane to drive the polarization diversity.We integrated one feed network on the second layer for the VP inverted-V dipole and the other feed network was integrated on the bottom layer (layer-4) for the HP inverted-V dipole.Additionally, the third layer was only inserted for rigidity and implementation purposes.Each feed network consisted of two 100 Ω lines with a phase difference of 180 • , and it was matched to a 50 Ω input impedance as shown in Figure 3.The admittances of the right and left arms of the feed network can be expressed by where G arm and jB arm denote the conductance and susceptance seen at each arm, respectively.Owing to the symmetric condition, the right and left arms of the feed network had an identical admittance.Using transmission lines, the conductance (or real value) of the input admittance looking into the end of transmission line could be transformed to 0.01 S with susceptance as follows.
where Garm and jBarm denote the conductance and susceptance seen at each arm, respectively.Owing to the symmetric condition, the right and left arms of the feed network had an identical admittance.Using transmission lines, the conductance (or real value) of the input admittance looking into the end of transmission line could be transformed to 0.01 S with susceptance as follows. 0.01 Then, an additional microwave stub could be used to eliminate the remaining susceptance of the input admittance.After transforming the input admittance to 0.01 S (i.e., impedance of 100 Ω), each line of the feed network could be connected to each arm of the inverted-V dipole.However, due to the strong coupling between the two crossed inverted-V dipoles, the impedance matching circuit needed to be further fine-tuned after realization.Since the radiation pattern of the proposed structure varied with respect to the height of the inverted arms, inclined angle, and length of each arm in the inverted-V dipole configuration, we performed the optimization process to determine each geometric parameter as described in Figure 2. First, in order to determine the optimized ground size, we simulated a single inverted-V dipole with respect to the changes in the ground plane size (Wgnd × Lgnd).The simulated radiation patterns on the xz-plane (referring to Figure 2b) for various ground sizes are shown in Figure 4a.For the purpose of faster simulation, the feed network was not included here and the optimized ground plane of 80 × 80 mm 2 (1.5λ0 × 1.5λ0 at 5.8MHz) was chosen for the broad beam pattern.Then, with the chosen ground plane size, the feed networks were included for the simulation.Referring to the geometric parameters of the feed network shown in Figure 2c, the stub sizes were optimized using impedance matching simulation as shown in Figure 4b.Then, an additional microwave stub could be used to eliminate the remaining susceptance of the input admittance.After transforming the input admittance to 0.01 S (i.e., impedance of 100 Ω), each line of the feed network could be connected to each arm of the inverted-V dipole.However, due to the strong coupling between the two crossed inverted-V dipoles, the impedance matching circuit needed to be further fine-tuned after realization.
Since the radiation pattern of the proposed structure varied with respect to the height of the inverted arms, inclined angle, and length of each arm in the inverted-V dipole configuration, we performed the optimization process to determine each geometric parameter as described in Figure 2. First, in order to determine the optimized ground size, we simulated a single inverted-V dipole with respect to the changes in the ground plane size (W gnd × L gnd ).The simulated radiation patterns on the xz-plane (referring to Figure 2b) for various ground sizes are shown in Figure 4a.For the purpose of faster simulation, the feed network was not included here and the optimized ground plane of 80 × 80 mm 2 (1.5λ 0 × 1.5λ 0 at 5.8 MHz) was chosen for the broad beam pattern.Then, with the chosen ground plane size, the feed networks were included for the simulation.Referring to the geometric parameters of the feed network shown in Figure 2c, the stub sizes were optimized using impedance matching simulation as shown in Figure 4b.Once the feed network and ground size were determined, we simulated the radiation patterns for the different inclined angles (θ) of inverted-V arms as shown in Figure 5a.Since the half-power beamwidth (HPBW) characteristic changes according to the angle variation, we chose the optimized angle of 45° for the proposed structure to ensure the broad beam pattern.Then, we simulated the effect of the height of the inverted-V arms, as shown in Figure 5b.Here, the simulated result showed a strong dependency of the peak gain and HPBW on the height, resulting in the optimized height of 13 mm for the proposed structure.Lastly, we optimized the width and length of the inverted-V arms using the simulated radiation patterns as shown in Figures 5c and 5d, respectively.If the width and length of the arms become too large, the effect of the ground reflector for the inverted-V configuration decreases.Therefore, to optimize the balance in peak gain and HPBW characteristics, we chose 5 mm for the width and 30 mm for the length.In addition, Figures 6a and 6b show the simulated radiation efficiency and total efficiency, respectively.At the center frequency of 5.8 GHz, the radiation efficiencies for the HP, VP, RHCP, and LHCP were about 94.3%, 92.5%, 93.1%, and 93.8%, respectively.According to Figures 6a and 6b, the total efficiency decreases faster with being away from the center frequency because of the integrated feed network.Since we designed both the antenna radiation element and the feed network with the same substrate, which had the relative permittivity of 2.5, the Once the feed network and ground size were determined, we simulated the radiation patterns for the different inclined angles (θ) of inverted-V arms as shown in Figure 5a.Since the half-power beamwidth (HPBW) characteristic changes according to the angle variation, we chose the optimized angle of 45 • for the proposed structure to ensure the broad beam pattern.Then, we simulated the effect of the height of the inverted-V arms, as shown in Figure 5b.Here, the simulated result showed a strong dependency of the peak gain and HPBW on the height, resulting in the optimized height of 13 mm for the proposed structure.Lastly, we optimized the width and length of the inverted-V arms using the simulated radiation patterns as shown in Figure 5c,d, respectively.If the width and length of the arms become too large, the effect of the ground reflector for the inverted-V configuration decreases.Therefore, to optimize the balance in peak gain and HPBW characteristics, we chose 5 mm for the width and 30 mm for the length.In addition, Figure 6a,b show the simulated radiation efficiency and total efficiency, respectively.At the center frequency of 5.8 GHz, the radiation efficiencies for the HP, VP, RHCP, and LHCP were about 94.3%, 92.5%, 93.1%, and 93.8%, respectively.According to Figure 6a,b, the total efficiency decreases faster with being away from the center frequency because of the integrated feed network.Since we designed both the antenna radiation element and the feed network with the same substrate, which had the relative permittivity of 2.5, the low permittivity of the feed network caused extra radiation, resulting in the reduction in total efficiency.The total efficiency could be further improved by fabricating the feed network with a high permittivity substrate, although the fabrication cost would also increase due to the use of multiple substrates.Finally, we summarized these design parameters based on the 3-D EM simulations in Table 1.low permittivity of the feed network caused extra radiation, resulting in the reduction in total efficiency.The total efficiency could be further improved by fabricating the feed network with a high permittivity substrate, although the fabrication cost would also increase due to the use of multiple substrates.Finally, we summarized these design parameters based on the 3-D EM simulations in Table 1.

Measurements
To verify the polarization diversity, we fabricated the proposed antenna with a Taconic TLX-9 substrate, which had a relative permittivity of 2.5. Figure 7 shows the implementation of the proposed inverted-V antenna with the design parameters summarized in Table 1.Two inverted-V antennas were fabricated in the crossed manner, and then they were integrated on the ground plane possessing the feed network as shown in Figure 7a.By using each input port at a time, the HP or VP could be generated.For CP verification, a 90 • phase difference with equal magnitude was required at both the HP and VP input ports.Thus, a 3-dB hybrid coupler was implemented and used as shown in Figure 7b, where we also summarized the measured S-parameters at 5.8 GHz.According to Figure 7b, the measured magnitude deviation was less than 0.4 dB and the measured phase deviation was less than 3.5 • at 5.8 GHz.Depending on the use of port 1 or port 4 of the hybrid coupler as an input port, the RHCP or LHCP could be excited.
Figure 8 shows the measured return characteristics and isolation characteristics in comparison to the simulation results for the crossed inverted-V antenna.The proposed antenna showed a measured 10-dB impedance bandwidth (IBW) of 752 MHz (5.376 GHz to 6.128 GHz).In addition, the isolation between the HP and VP input ports was about 20 dB at the target frequency of 5.8 GHz.
Figure 9 shows the simulated and measured radiation patterns for both the HP and VP on the xz and yz planes with good agreement.Table 2 summarizes the measured gain and HPBW for the HP and VP, as well as the measured gain and HPBW for the RHCP and LHCP.In addition, Table 2 also compares the ratios for gain to Q-factor.However, this ratio cannot be directly judged to reflect the electrical limitations like the electrically small antennas [28][29][30], since the proposed antenna has ka larger than 1.Finally, Figure 10 shows the simulated and measured radiation patterns with cross-polarization characteristics for both the RHCP and LHCP of the proposed antenna.
To compare the characteristics of the proposed antenna, we summarized some of the state-of-the art crossed dipole antenna configurations in Table 3.Here, the antenna volume denotes the radiation element's pure volume excluding the ground plane size.The antennas in References [16,17] had conducting walls surrounding the radiation elements, thereby achieving high gains.However, the HPBW was sacrificed and extra conducting walls were required.Moreover, only a single type of polarization was verified in References [16,17,19].Therefore, the proposed antenna overall showed an excellent qualification for IoT applications whilst possessing polarization diversity, compactness in size, and reasonable gain.
For CP verification, a 90° phase difference with equal magnitude was required at both the HP and VP input ports.Thus, a 3-dB hybrid coupler was implemented and used as shown in Figure 7b, where we also summarized the measured S-parameters at 5.8 GHz.According to Figure 7b, the measured magnitude deviation was less than 0.4 dB and the measured phase deviation was less than 3.5° at 5.8 GHz.Depending on the use of port 1 or port 4 of the hybrid coupler as an input port, the RHCP or LHCP could be excited.Figure 8 shows the measured return characteristics and isolation characteristics in comparison to the simulation results for the crossed inverted-V antenna.The proposed antenna showed a measured 10-dB impedance bandwidth (IBW) of 752 MHz (5.376 GHz to 6.128 GHz).In addition, the isolation between the HP and VP input ports was about 20 dB at the target frequency of 5.8 GHz. Figure 9 shows the simulated and measured radiation patterns for both the HP and VP on the xz and yz planes with good agreement.Table 2 summarizes the measured gain and HPBW for the HP and VP, as well as the measured gain and HPBW for the RHCP and LHCP.In addition, Table 2 also compares the ratios for gain to Q-factor.However, this ratio cannot be directly judged to reflect the electrical limitations like the electrically small antennas [28][29][30], since the proposed antenna has ka larger than 1.Finally, Figure 10 shows the simulated and measured radiation patterns with cross- xz and yz planes with good agreement.Table 2 summarizes the measured gain and HPBW for the HP and VP, as well as the measured gain and HPBW for the RHCP and LHCP.In addition, Table 2 also compares the ratios for gain to Q-factor.However, this ratio cannot be directly judged to reflect the electrical limitations like the electrically small antennas [28][29][30], since the proposed antenna has ka larger than 1.Finally, Figure 10 shows the simulated and measured radiation patterns with crosspolarization characteristics for both the RHCP and LHCP of the proposed antenna.To compare the characteristics of the proposed antenna, we summarized some of the state-ofthe art crossed dipole antenna configurations in Table 3.Here, the antenna volume denotes the radiation element's pure volume excluding the ground plane size.The antennas in References [16,17] had conducting walls surrounding the radiation elements, thereby achieving high gains.However, the HPBW was sacrificed and extra conducting walls were required.Moreover, only a single type of

Conclusions
This article proposed a compact crossed inverted-V antenna with reconfigurable polarization characteristics.The proposed antenna could generate four different types of polarizations (VP, HP, RHCP, and LHCP), and it was analyzed using both 3-D EM simulations and measurements at 5.8 GHz.To verify the polarization diversity performance, we fabricated the proposed antenna with a Taconic TLX-9 substrate, which had a relative permittivity of 2.5.The overall volume of the proposed antenna including the whole ground plane was 80 × 80 × 15 mm 3 .The antenna showed a measured 10-dB impedance bandwidth of 752 MHz (5.376 GHz to 6.128 GHz).The peak gains for the VP, HP, RHCP, and LHCP operations were about 5.2 dBi, 4.61 dBi, 5.25 dBic, and 5.51 dBic, respectively, at 5.8 GHz.In addition, the HPBWs for all the polarizations were greater than 78 • .

Figure 1 .
Figure 1.Multiple-input multiple-output (MIMO) communication of IoT sensors or devices through (a) a single polarization, and (b) polarization diversity (horizontal, vertical, right-hand circular, and left-hand circular polarizations).

Figure 1 .
Figure 1.Multiple-input multiple-output (MIMO) communication of IoT sensors or devices through (a) a single polarization, and (b) polarization diversity (horizontal, vertical, right-hand circular, and left-hand circular polarizations).

Figure 2 .
Figure 2. The proposed antenna structure with: (a) a 3-dimensional view, (b) a single inverted-dipole, and (c) a multi-layered feed network and layer information.

Figure 2 .
Figure 2. The proposed antenna structure with: (a) a 3-dimensional view, (b) a single inverted-dipole, and (c) a multi-layered feed network and layer information.

2 )
y R = y L = 0.01 + jB (Electronics 2019, 8, x FOR PEER REVIEW 4 of 11 to a 50 Ω input impedance as shown in Figure 3.The admittances of the right and left arms of the feed network can be expressed by

Figure 3 .
Figure 3. Antenna feed network with tuning stubs for a single inverted-V dipole.

Figure 3 .
Figure 3. Antenna feed network with tuning stubs for a single inverted-V dipole.

Figure 4 .
Figure 4. Simulation for (a) the radiation patterns on the xz-plane according to different ground plane sizes, and the smith chart impedance matching using the (b) ystub (horizontal) and (c) Lstub (horizontal) of the feed network, referring to Figure 2 (c), at 5.8GHz.

Figure 4 .
Figure 4. Simulation for (a) the radiation patterns on the xz-plane according to different ground plane sizes, and the smith chart impedance matching using the (b) ystub (horizontal) and (c) Lstub (horizontal) of the feed network, referring to Figure 2c, at 5.8 GHz.

Figure 5 .
Figure 5. Simulated radiation patterns according to the different (a) inclined angle, θ, on the xz-plane (b) height, h, on the yz-plane, (c) width, Warm, on the xz-plane, and (d) length, Larm, on the xz-plane of the inverted-V arms.Here, different radiation planes are plotted for the best view of variation.

Figure 5 .
Figure 5. Simulated radiation patterns according to the different (a) inclined angle, θ, on the xz-plane (b) height, h, on the yz-plane, (c) width, Warm, on the xz-plane, and (d) length, Larm, on the xz-plane of the inverted-V arms.Here, different radiation planes are plotted for the best view of variation.

Figure 5 .
Figure 5. Simulated radiation patterns according to the different (a) inclined angle, θ, on the xz-plane (b) height, h, on the yz-plane, (c) width, Warm, on the xz-plane, and (d) length, Larm, on the xz-plane of the inverted-V arms.Here, different radiation planes are plotted for the best view of variation.

Figure 6 .
Figure 6.Simulated (a) radiation efficiency and (b) total efficiency over the operation frequencies.

Figure 7 . 11 Figure 7 .
Figure 7. Implementation of the proposed crossed inverted-V antenna for the (a) horizontal polarization (HP) and vertical polarization (VP) test, and (b) the right-hand circular polarization (RHCP) and the left-hand circular polarization (LHCP) test with an additional 3-dB hybrid coupler.

Figure 8 .
Figure 8. Simulated and measured (a) return and (b) isolation characteristics.

Figure 8 .
Figure 8. Simulated and measured (a) return and (b) isolation characteristics.

Figure 9 .
Figure 9. Simulated and measured radiation patterns: (a) HP and (b) VP on both the xz and yz planes.

Figure 9 .
Figure 9. Simulated and measured radiation patterns: (a) HP and (b) VP on both the xz and yz planes.

Figure 10 .
Figure 10.Simulated and measured radiation patterns with cross-polarization characteristics for the (a) RHCP on the xz-plane, (b) RHCP on the yz-plane, (c) LHCP on the xz-plane, and (d) LHCP on the yz planes.

Figure 10 .
Figure 10.Simulated and measured radiation patterns with cross-polarization characteristics for the (a) RHCP on the xz-plane, (b) RHCP on the yz-plane, (c) LHCP on the xz-plane, and (d) LHCP on the yz planes.

Table 1 .
Design parameters of the proposed inverted-V antenna.Wstub denotes the width of the stubs used in the feed network. *

Table 2 .
Measured gain, the half-power beamwidth (HPBW), and Gain/Q ratio of the proposed antenna.

Table 3 .
Comparison table with the previously reported crossed-dipole structure.λ o denotes the free-space wavelength at the center frequency. *