Sea Echoes for Airborne HF/VHF Radar: Mathematical Model and Simulation

: Currently, shore-based HF radars are widely used for coastal observations, and airborne radars are utilized for monitoring the ocean with a relatively large coverage offshore. In order to take the advantage of airborne radars, the theoretical mechanism of airborne HF/VHF radar for ocean surface observation has been studied in this paper. First, we describe the ocean surface wave height with the linear and nonlinear parts in a reasonable mathematical form and adopt the small perturbation method (SPM) to compute the HF/VHF radio scattered ﬁeld induced by the sea surface. Second, the normalized radar cross section (NRCS) of the ocean surface is derived by tackling the ﬁeld scattered from the random sea as a stochastic process. Third, the NRCS is simulated using the SPM under different sea states, at various radar operating frequencies and incident angles, and then the inﬂuences of these factors on radar sea echoes are investigated. At last, a comparison of NRCS using the SPM and the generalized function method (GFM) is done and analyzed. The mathematical model links the sea echoes and the ocean wave height spectrum, and it also offers a theoretical basis for designing a potential airborne HF/VHF radar for ocean surface remote sensing.


Introduction
The sea echoes of HF or VHF ocean radars contain rich information about the sea surface since the length of the HF/VHF radio wave is very close to the wave length of gravity wave at the ocean surface [1]. On the one hand, shore-based HF radars are important components of coastal operational monitoring systems [2][3][4]. Many countries have utilized shore-based HF radars to obtain ocean current, wind and wave fields [5,6]. The maximum detection range of shore-based HF radars can reach 250 km, with the time resolution ranging from 10 min to 1 h and the spatial resolution varying from 300 m to 5 km. On the other hand, along with the development of electronic technology, airborne radars have been widely used for ocean remote sensing [7][8][9]. The size of radar is becoming smaller, and the cost of developing airborne radars is lower. In addition, an airborne VHF radar has been developed for forest remote sensing [10]. All these developments make it possible to design and develop an airborne HF/VHF radar to monitor the sea surface. The objective of this paper is to investigate the interaction mechanism of HF/VHF electromagnetic waves scattering from the ocean's surface, and this should provide a theoretical basis for designing novel airborne HF/VHF radars for ocean remote sensing.
Many scholars have analyzed the interaction mechanism between HF/VHF electromagnetic waves and ocean waves for shore-based HF radar. Barrick [11] adopted the small perturbation method (SPM) to compute the scattered field from the time-varying sea surface and derived the normalized radar cross section (NRCS) of the sea surface for monostatic HF radar. Subsequently, Johnstone [12] and Anderson [13] respectively extended Barrick's work to the configuration of shore-based bistatic HF radar. For the SPM, Hisaki [14] considered the effect of finite illumination area to derive the NRCS for shore-based monostatic HF radar. More recently, Hardman et al. [15] also presented the shore-based bistatic NRCS utilizing the SPM. Besides that, Srivastava and Walsh [16,17] proposed a generalized function method (GFM) to analyze the scattered field from the sea surface and derived the NRCS for the shore-based monostatic HF radar. Afterwards, the GFM was also extended to derive the NRCS for the shore-based bistatic HF radar [18][19][20]. It is noted that Silva et al. [21] modified the usual way of the GFM and derived a more general NRCS of the sea surface with arbitrary sea states.
For airborne HF/VHF radar, Bernhardt et al. [22,23] proposed the concept of HF Ground-Ionosphere-Ocean-Space (GIOS), and conducted experiments to observe the sea surface. Anderson [24] proposed the airborne passive HF radar which can be used to monitor the sea. Later, Chen et al. [25,26] theoretically analyzed the sea echoes of the shore-to-air bistatic HF radar. Meanwhile, Voronovich and Zavorotny [27] proved the possibility of extracting the wave height spectrum using airborne HF/VHF radars.
However, the theoretical study on the airborne HF/VHF radar is still in an initial stage. Voronovich and Zavorotny [27] analyzed the first-order interaction between HF/VHF radio waves and ocean waves, but they omitted the second-order information which is much more complicated than the first-order interaction and crucial for investigating the interaction mechanism between the HF/VHF radio waves and ocean surface waves. This paper analyzes the first-and second-order interactions which occur in the scattering of HF/VHF electromagnetic waves from the sea surface. First, a big square area of the sea surface is considered as the scattering patch. Taking into account the randomness of the sea surface, the ocean surface wave height is represented as the superposition of linear and nonlinear wave heights. Next, the SPM is employed to derive the scattered field from the sea surface. Then we obtain the NRCS of the sea surface for airborne HF/VHF radars. Finally, the theoretical NRCS of the sea surface is simulated with various parameters, such as sea states and radar operating frequencies.
This paper is organized as follows. Section 2 gives the description of the calculation of the scattered field. In Section 3, the NRCS of the sea surface is derived. Section 4 consists of the simulation of the NRCS and the analysis of the simulated sea echoes. Discussion and conclusions are presented in Sections 5 and 6, respectively.

The Review of the Description of Wave Heights
As shown in Figure 1, the geometry of the scattering patch is established using a three-dimensional Cartesian coordinate system, and the center of the scattering patch is set as the origin. The scattering patch is assumed to be a square area with a very large side length of L. The x axis is assumed as the projection direction of radar beam at the sea surface and the y axis is at the sea surface and perpendicular to the x axis. The z axis is vertical to the sea surface.
Then the sea surface wave height z = f (x, y, t) can be expressed by Fourier series as: where m, n and l are integers between −∞ and +∞, a = 2π/L and w = 2π/T; t denotes time; T is the temporal period of the Fourier expansion; f (1) (x, y, t) and f (2) (x, y, t) are Fourier series which denote linear and nonlinear wave heights [28], respectively; the superscripts 1 and 2 denote the first-order and second-order terms in the perturbational analysis, respectively; p 1 (m, n, l) and p 2 (m, n, l) are the Fourier coefficients of the linear and nonlinear wave heights, respectively. Figure 1. The geometry of the scattering patch. The square scattering patch is represented by the parallelogram whose sides are navy blue straight lines. The radar is located in the far zone of the scattering patch (R 0 L). Backscattering is considered, i.e., θ i = θ s . Here the x-z plane is perpendicular to the sea surface and contains the center of the scattering patch and the point of the radar position. k i and k s represent the wave vectors of the incident and scattered fields, respectively.
When perturbational analysis is utilized to solve the hydrodynamic equations, it is found that p 2 (m, n, l) can be expressed using p 1 (m, n, l) [28]: where m , n and l are integers between −∞ and +∞; g is the gravitational acceleration; k and k represent two ocean wave vectors; ω and ω are the angular frequencies corresponding to k and k , respectively. If k = − k and ω = −ω , Γ( k , ω , k , ω ) = 0; otherwise where | k | and | k | are the lengths of k and k , respectively. The angular frequencies ω 0 = ± g| k | and ω 0 = ± g| k | are given by the dispersion relationship of the gravity waves in deep water.

Statistical Characteristics of the Scattering Patch
According to [29], the Fourier coefficient p 1 (m, n, l) of linear wave height can be considered as a Gaussian random variable so that (1)-(3) can represent a real random sea surface. The mean of the random variable p 1 (m, n, l) is zero: where < · · · > denotes a statistical ensemble average. p 2 (m, n, l) is also a random variable, because p 2 (m, n, l) is determined by random variable p 1 (m, n, l).
The linear wave height f (1) (x, y, t) can be regarded as a stationary random process, so the power spectral density of the linear wave height is calculated as: where τ x = x 1 − x 2 , τ y = y 1 − y 2 , τ = t 2 − t 1 and f (1) * (x 2 , y 2 , t 2 ) means the complex conjugation of f (1) (x 2 , y 2 , t 2 ). W(p, q, ω) is called the spatial-temporal spectrum of ocean waves. p and q denote the components of a ocean wave vector k along the x axis and y axis, respectively. ω is the angular frequency corresponding to k. After calculation, the relationship between W(p, q, ω) and p 1 (m, n, l) is where ( k, ω) = (p, q, ω) = (am, an, wl). The spatial-temporal spectrum W(p, q, ω) also can be expressed as where δ(·) is the Dirac delta function, and S( k) is the directional wavenumber spectrum.

The Incident and Scattered Fields Near the Sea Surface
Now we assume the incident field arriving at the scattering patch is vertically polarized with an incidence angle of θ i . The wave vector k i = (k 0 sin θ i , 0, −k 0 cos θ i ) of the incident electromagtic wave is shown in Figure 1. Then the incident plane wave near the scattering patch, E i , can be expressed as: where E 0 is the magnitude of the electric field intensity of the incident field; ω c and k 0 are the angular frequency and wavenumber corresponding to the radio frequency f c in the free space, respectively;x, y andẑ are unit vectors along each coordinate axis; E i x , E i y and E i z are the components of E i along the x, y and z axes, respectively.
In (1)-(3), the whole sea surface has been treated as a periodic repetition of the scattering patch. In this way, the scattered field near the scattering patch can be derived using the SPM, which is a classical way to calculate the scattered field generated by periodic rough surface.
The slightly rough sea surface within the scattering patch can be divided into two parts: one is the planar part of the surface, and the other is the rough part of the surface. Consequently, the scattered field near the scattering patch contains two parts: the field induced by the planar surface, , and the field caused by the rough surface, E sr = E sr xx + E sr yŷ + E sr zẑ .
With the assumption that the sea water is an ideal conductor and the incident field is a plane wave at a frequency of f c , the total electric field intensity, E t = E t xx + E t yŷ + E t zẑ , near the scattering patch, can be expressed as: The scattered field induced by the planar part is The components E sr x , E sr y and E sr z of the scattered field induced by the rough part are expressed as Fourier series: where A(m, n, l), B(m, n, l) and C(m, n, l) are unkown Fourier coefficients. E(m, n, l) is assumed as: The coefficients A(m, n, l), B(m, n, l) and C(m, n, l) can be derived by expanding boundary conditions in perturbation parameter or smallness [30]. Here f (1) (x, y, t) and f (2) (x, y, t) are selected as the firstand second-order smallness, respectively. Two boundary conditions must be satisfied. First, the tangential component of the total electric field intensity is zero at the interface between the sea water and the air, because the sea water is perfectly conducting. Second, the divergence of the total electric field intensity is zero, because the zone above the sea surface is sourceless. Then substituting the components E t x , E t y and E t z of the total electric field into these two boundary conditions gives the first-and second-order solutions of A(m, n, l), B(m, n, l) and C(m, n, l). The results are presented in (18)- (25) where av = sin θ i with an integer v is assumed to facilitate the calculation. A (1) (m, n, l), B (1) (m, n, l) and C (1) (m, n, l) are the first-order solutions. A (2) (m, n, l), B (2) (m, n, l) and C (2) (m, n, l) are the second-order solutions. Substituting these Fourier coefficients into E sr x , E sr y and E sr z , the total electric field near the sea surface can be obtained. Referring to Barrick's work [31], the first-and second-order terms of the scattered field are caused by the first-and second-order Bragg scattering, respectively.

The Scattered Field Far from the Scattering Patch
For airborne HF radars, the antennas are located in the far zone of the scattering patch. As shown in Figure 1, the far zone means that the distance R 0 between the radar antenna and the center of the scattering patch is much longer than the side length L of the scattering patch.
Here the Stratton-Chu integral is employed to calculate the scattered field in the far zone of the scattering patch [12,32]. For monostatic configuration, substituting the scattered field from the rough part of the scattering patch into the Stratton-Chu integral gives (26), which represents the scattered field H f (R 0 , t) at the receive antenna.
In (26), H sr denotes the magnetic field corresponding to E sr ; is the integration interval of the Stratton-Chu integral;n =ẑ is the unit normal vector of the integration plane; r = (x, y, z) is the vector pointing from the center of the scattering patch to any point in the integration area; 0 and µ 0 are the electrical and magnetic permittivity of free space, respectively. For backscattering, the angle of reflection θ s is identical to the angle of incidence θ i , i.e., θ i = θ s . As mentioned in [14,15], when L is very big, i.e., L → +∞ is assumed, the integration interval of the Stratton-Chu integral can also be set as The results of the NRCS are the same for these two cases of the integration interval.
As shown in Figure 1, the antenna locates at the point (R 0 , θ s = θ i , φ s = π) in the spherical coordinate system. The vertical polarization is considered herein. Thus the vertically polarized component along the direction φ s = π in the spherical coordinate system: where τ = t 2 − t 1 . 2. Estimate the power spectral density. Take the Fourier transform of R(τ) and estimate the power density spectrum R(ω ): 3. Calculate the normalized power spectral density. The normalized power density spectrum σ(ω ) is derived by: where H 0 = E 0 0 /µ 0 is the magnitude of the magnetic field intensity corresponding to the magnitude of the electric field intensity of the incident field. σ(ω ) is also called the NRCS of the sea surface. The normalization is applied to derive the range-independent NRCS at the sea surface area.
For an airborne HF/VHF radar, σ(ω ) is a function of the incidence angle θ i . For that ω d = ω − ω c is the Doppler frequency, σ(ω ) is rewritten as σ(ω d , θ i ) which is given in (32)- (34). The definitions of the coefficients and vectors in (32)-(34) are given in (35)-(41). Here the velocity of airplane is assumed to be constant within the coherent integration time and has been left out.
There is a singularity in the denominator of Γ EM when k 2 0 cos 2 θ i + k 1 · k 2 becomes zero. The assumption that the sea water is perfectly conducting causes the singularity. A term, −k 0 ∆, is added in the denominator of Γ EM to eliminate this singularity [12,33]. ∆ is the normalized surface impedance which is a complex constant, i.e., ∆ = 0.011 − i(0.012). The added term −k 0 ∆ means the small energy loss of HF electromagnetic waves traveling along the actual sea surface which is good at conducting rather than perfectly conducting.

The Effectiveness of the NRCS
The NRCS of the sea surface has been derived using the SPM. Accordingly, the approximation made in the perturbational analysis must satisfy the condition: where h is the root mean square (RMS) wave height of the sea surface, k 0 is the wavenumber of the incident plane wave at a frequency of f c and θ i is the incident angle [28,34]. To ensure the correctness of the results from the perturbational analysis, a more rigorous condition is adopted in this work: Considering that h s = 4h (h s is significant wave height), the NRCS σ(ω d , θ i ) is effective only if the following inequality is satisfied: where G( f c ) is defined as: The scattered field induced by the rough part of the sea surface is taken into consideration herein. As a result, the NRCS σ(ω d , θ i ) is effective only when the angle of incidence θ i satisfies 20 • ≤ θ i ≤ 90 • where the intensity of the scattered field from the plane part of the sea surface is much smaller than the intensity of the scattered field from the rough part of the sea surface [31]. Figure 2 shows the effective region of the NRCS σ(ω d ,

The Simulation and Analysis of the Sea Echo
The interpretation of the NRCS of the sea surface is crucial to analyze the sea echoes. The NRCS of the sea surface, σ(ω d , θ i ), is interpreted as the theoretical prediction of the sea-echo Doppler spectrum. Consequently, the simulations of σ (1) (ω d , θ i ) and σ (2) (ω d , θ i ) are treated as the first-and second-order sea-echo Doppler spectra, respectively. It can be found from the Formulas (32)-(34) that the directional wavenumber spectrum S( k) is included in the theoretical sea-echo Doppler spectrum σ(ω d , θ i ). S( k) is the product of a non-directional wave spectrum S(k) and a directional distribution function g(α). It is assumed that only wind waves exist and they are fully developed. The Pierson-Moskowitz spectrum [35] and the cardioid distribution model [33] are assumed: where U is the wind speed at 19.5 m above the sea surface and α is the dominant wave direction which is the same with wind direction for wind-wave sea state. The relationship between U and h s is: It can be seen that the theoretically predicted sea-echo Doppler spectrum σ(ω d , θ i ) is influenced by four factors: the dominant wave direction α , the incident angle θ i , the radar frequency f c and the sea state h s . Here we investigate the effects of the latter three factors on σ(ω d , θ i ). For simplification, a normalized Doppler frequency is defined as η = ω d /ω B in the simulation. It is easy to prove that when θ i = 90 • , the theoretical sea-echo Doppler spectrum σ(ω d , θ i ) is reduced to the classical NRCS for shore-based HF radar.

Sea Echoes at Different Radar Frequencies and Sea States
When α = 90 • , different values of f c , θ i and h s are selected to simulate the Doppler spectrum. The simulated results for θ i = 30 • , 45 • , 55 • and 70 • are given in Figures 3-6, respectively. Each sub-figure in Figures 3-6 corresponds to a combination of θ i and h s and shows the Doppler spectrum at six radar frequencies, i.e., f c = 3,9,15,30,45 and 55 MHz. The first-order sea-echo Doppler spectrum σ (1) (ω d , θ i ) is represented by the two peaks at η = ±1, and the continuous curves around these two peaks are the second-order sea-echo Doppler spectra σ (2) First, as shown in Figure 3, the symmetry characteristics of the simulated results (when α = 90 • and θ i = 90 • ) are the same as the simulated sea-echo Doppler spectra for shore-based HF radar (when α = 90 • and θ i = 90 • ) [33].
Second, it is noted that the first-order sea-echo Doppler spectrum seems a constant for each θ i when the radar works in a higher frequency band, e.g., f c ≥ 15 MHz. It can be found from Figures 3a, 4a, 5a and 6a that the energy of the first-order peak is relatively smaller when radar frequency is low and sea state is calm, e.g., f c = 3 MHz and h s = 0.7 m. The reason for this is that the energy of ocean waves which cause the first-order Bragg scattering does not vary dramatically when f c is high and h s is large.
Finally, it can be seen from Figure 3a-d that the second-order spectrum increases in magnitude when f c increases. However, when the values of f c and h s do not meet the condition given in (44), the second-order spectrum is even higher than the first-order peaks. As mentioned in [33], in this case, the theoretical Doppler spectrum predicted by the SPM is not accurate.
For each pair of θ i and h s , six radar frequencies were selected to simulate the spectra. The six values of f c were 3, 9, 15, 30, 45 and 55 MHz. The dominant wave direction α is 90 • .

Sea Echoes for Different Incidence Angles
Comparing Figures 3a, 4a, 5a and 6a, it can be found that the first-order spectrum σ (1) (ω d , θ i ), which is represented by the two highest peaks in the spectra, varies with θ i . To make it clear, the values of σ (1) (ω d , θ i ) dω d against incident angles are shown in Figure 7a, and it shows that the radar-received energy caused by the first-order Bragg scattering drops from −11 dB to −23 dB when θ i increases from 20 • to 90 • .
As shown in Figure 7b, this descending trend also exists in the second-order Doppler spectra for different θ i . For |η| < 1, the values of second-order spectra decrease nearly 10 dB when θ i varies from 25 • to 90 • . In contrast, for |η| > 1, the magnitude of the second-order spectrum decreases even more than 10 dB. Figure 7c demonstrates the value of σ However, this descending trend is not significant for the near-grazing case, i.e., for 70 • ≤ θ i ≤ 90 • . The value of σ (1) 0 drops less than 1 dB when θ i changes from 70 • to 90 • . The second-order Doppler spectrum for θ i = 70 • is nearly identical to that for θ i = 90 • . Consequently, the values of σ (2) 0 for θ i = 70 • and 90 • are nearly equal. There are two reasons for this phenomenon. One reason is that the values of the functions sin θ i and cos θ i vary slightly with θ i changing from 70 • to 90 • , which causes a small variation in the length of the vector −2 sin θ i k 0 . The other one is that the ocean waves which cause the second-order Bragg scattering contain nearly equal energy for 70 • ≤ θ i ≤ 90 • .

Sea Echoes for Different Sea States
In Section 4.1, it has been clearly seen that the first-order Doppler spectra do not vary as the sea state becomes higher. Here it is necessary to investigate the variation of the second-order spectrum when sea state is higher. As shown in Figure 8, the Doppler spectra under three different sea states (h s = 1.3 m, 2.92 m and 4.56 m) for different angles of incidence (θ i = 25 • , 55 • and 90 • ) were simulated while α = 45 • and f c = 8 MHz. It is obvious that the energy of the second-order Doppler spectrum becomes stronger along with the higher sea state.

Comparison between SPM and GFM
For the case of shore-based monostatic HF radar, both the SPM [31] and GFM [16] have been utilized to derive the NRCS of the sea surface. For a comparison between these two methods, it is convenient to simulate the sea echoes derived by the two methods. Under the same condition as Figure 5 in [36], we simulated the model which was derived by using the SPM. The simulated result is shown in Figure 9. It is seen that the Doppler spectra simulated by the two methods are similar in shape. Each result shows that the positive first-order peak is nearly 10 dB larger than the negative one. However the amplitudes of these two spectra are not equal. As mentioned in [36], these two methods are different although they have the same form. The significant difference is that the NRCS based on the GFM is affected by the range resolution of the radar while the NRCS derived using the SPM is not based on this parameter.
The above comparison shows a typical example of the NRCSs simulated using the GFM and the SPM. However, a recent work [21] seems to indicate that the derivation of the NRCS using the GFM has a wider application range in terms of approximation restrictions. The derivation of the NRCS using the SPM is on the basis of three assumptions: first, the sea water is a good conductor; second, the slope of ocean surface wave height is much smaller than 1; third, the product of the significant wave height and the radio wavenumber is small. The results in Figures 3-8 were obtained based on those conditions. Additionally, HF radar NRCS simulated using the SPM has been validated using real data for more than 50 years. In contrast, it is possible to remove the significant wave height restriction using the GFM as shown in [21]. In that work, the NRCS with arbitrary roughness scales has been obtained, but it has not been compared with real Doppler spectrum.

Discussion
Four factors, radar frequency f c , the angle of incidence θ i , the significant wave height h s and the dominant wave direction α , which influence the shape and the magnitude of the sea-echo Doppler spectrum, have been investigated.
First, it was found that the first-and second-order spectra increase when radar frequency becomes higher. However, the Doppler spectrum becomes saturated when radar frequency is too high to meet the effective condition of the SPM. From the radar equation, we know that SNR o ∝ P t σ 0 /L p , where SNR o is the signal to noise ratio at the output of the radar receiver, P t is the transmitted power of radar, σ 0 = 1 2 +∞ −∞ σ(ω d , θ) dω d and L p represents the propagation loss of radio waves. If radar frequency increases, both the L p and σ 0 vary. Thus, it is much better to combine the σ 0 (derived in this paper) with a suitable L p (which is not the focus of our work) to select radar frequency for designing an airborne HF/VHF radar for ocean remote sensing.
Second, the variation that occurs in the sea-echo Doppler spectrum when θ i changes attracts our attention. It can be known from Figure 7a,c that σ 0 increases nearly 10 dB with θ i changing from 90 • to 20 • (σ 0 = σ (1) 0 + σ (2) 0 ). The σ 0 becomes large when the incident angle becomes small, and L p is smaller when radio waves propagate in the air than when they propagate along the air-sea surface. Consequently, considering the same SNR o for the airborne HF/VHF radar and the shore-based HF radar, P t could be much smaller for airborne HF/VHF radars. It is convenient to design a relatively compact and low-power airborne HF/VHF radar.
Third, the energy of the sea echo increases when the sea state becomes higher, which is similar to the case of shore-based HF radar.
Finally, since the NRCS connects the sea echoes and the waveheight spectrum, it is possible to retrieve wave parameters from radar sea echoes by inversing the NRCS. In addition, sea surface current may also be extracted from the first-order echoes by determining the Doppler shift induced by current. The difference between θ i = 90 • and θ i = 90 • for current inversion is shown in Figure 10. If airborne and shore-based HF radars are located at the positions as the red points in the picture, the current velocity measured by the shore-based HF radar is V x , whereas the current measured by the airborne radar is V which is a component of V x .

Conclusions
In this paper, the sea surface wave height has been expressed as the superposition of two Fourier series which represent linear and nonlinear wave heights. Then the SPM was adopted to get the scattered field from the sea surface. The scattered field has been calculated by taking into account both the first-and second-order Bragg scatterings between the sea surface waves and the electromagnetic waves. At last, theoretical models of the first-and second-order sea-echo Doppler spectra for the airborne HF/VHF radars have been derived. Besides that, the effectiveness region of the theoretical sea-echo Doppler spectrum σ(ω d , θ i ) was given.
There are continuous second-order spectra σ (2) (ω d , θ i = 90 • ) around the first-order Bragg peaks σ (1) (ω d , θ i = 90 • ) in the sea-echo Doppler spectra of the shore-based HF radar, and the continuous spectra have been used for wave parameter inversion in practice. Thus, the second-order terms in the SPM are not neglected in order to get the theoretical second-order sea-echo Doppler spectrum for the airborne HF/VHF radar. Both the first-and second-order spectra were simulated under different environment conditions to give a brief demonstration of the sea echo is received by radar. In addition, the results of the simulated sea echoes may provide a basic guide for designing an airborne HF/VHF radar to monitor the sea state in the future.

Conflicts of Interest:
The authors declare no conflict of interest.

Abbreviations
The following abbreviations are used in this manuscript: HF high frequency VHF very high frequency NRCS normalized radar cross section SPM small perturbation method GFM generalized function method GIOS Ground-Ionosphere-Ocean-Space RMS root mean square