Experimental Validation of Different Control Techniques Applied to a Five-Phase Open-End Winding Induction Motor

: Open-end winding ﬁve-phase induction motor (OeW-5PIM) conﬁguration is used in industrial applications, where minimization in the total harmonic currents and high reliability are needed. The majority of the literature on OeW-5PIM topology discusses ﬁeld-oriented control and direct torque control in addition to other robust control techniques such as the backstepping approach. This paper focuses on the mathematical and experimental approaches of backstepping control (BSC) and rotor-ﬂux-oriented control (RFOC) for an OeW-5PIM topology. The space vector pulse width modulation (SVPWM) strategy is associated with the suggested control techniques to improve the dynamic performance (i.e., reducing ripple, ﬁxed switching frequency, etc.) of the studied motor. Furthermore, the RFOC-SVPWM and BSC-SVPWM are comprehensively compared using experimental implementation under various situations such as load torque, open-phase fault, and high/low-speed operation.


Introduction
Recently, multilevel inverter configurations have been widely employed for medium/high-voltage drive systems due to their inherent advantages such as sinusoidal output currents, reduced switching losses and lower dv/dt in the output voltages, etc. [1][2][3][4][5]. On the other hand, multiphase machines' topology has gained interest during the last couple of decades because of their inherent benefits when compared to equivalent three-phase counterparts, such as higher robustness, lower rotor harmonic voltages, higher density of power, lower torque pulsations, better fault tolerance, higher redundancy, and greater degrees of freedom [6][7][8][9][10][11][12][13]. Therefore, it appears that multiphase machines are a strong competitor, especially in demanding high-power applications like aerospace, electric aircraft, railway traction, wind-energy conversion, ship propulsion, and other industrial applications where great reliability and redundancy are essential [9,[14][15][16]. Due to these inherent benefits, it is feasible to combine the advantages of both structures by just using the open-end winding (OeW) structure with multilevel inverters for multiphase motor drives [2,4,5,7,[17][18][19][20][21][22], where the desired configuration can be achieved by opening the neutral point of the 5PIM drive and powering both ends of the windings of the stator with a dual inverter. Due to the various benefits it possesses over a star-connected machine, the OeW design has attracted interest because of its features, such as its lower voltage stress on power switches, reduced dc-link current, multi-level waveform, higher power 1.
Different control techniques are designed and analyzed to ensure the robustness of an OeW-5PIM drive against uncertainties and load torque that are usually present in real systems.

3.
A comprehensive comparison and performance analysis is accomplished between the BSC and RFOC strategy. 4.
The validation of the proposed control strategies is achieved using experimental implementation, which demonstrates the improved performance of the suggested strategies under different situations of operation.
This paper is organized as follows: Section 2 provides the 5PIM model as well as giving a review of the OeW-5PIM structure. Section 4 presents the RFOC strategy. Section 3 develops the BSC approach of the OeW-5PIM topology. Section 5 discusses the real-time results and comparison between the two control strategies. Finally, Section 6 provides a conclusion to the paper that has been presented.

Description of the Studied Motor Topology
This section describes the development of the 5PIM model as well as giving a review of the OeW-5PIM structure.

Modeling of the 5PIM Drive
The 5PIM model based on the field orientation law is presented in (d-q-x-y) frames, where the direct rotor flux is ϕ rd = ϕ r and the quadratic rotor flux is supposed to be zero ϕ rq = 0 [4], which are represented as follows [2]: Consequently, the developed torque formulation is as follows: where i sd , i sq , i sx , and i sy denote the stator current components; V sd , V sq , V sx , and V sy are thevoltage components; T r is the rotor time constant; L ls and L lr are the rotor/stator leakage inductances, respectively; L sr is the magnetizing inductance; F is the viscous friction coefficient; and J is the rotor inertia. Also:

Electric Circuit of the OeW Configuration
The electric circuit of a 5PIM supplied by a dual-voltage source inverter (VSI) (VSI-a and VSI-b) with a separate DC is depicted in Figure 1 and will be examined in this study. On the other side, each inverter has two switches with their anti-parallel diodes. Moreover, each inverter possesses32 possible switching pulses [4]. As a consequence, as illustrated in Figure 2, there are 30 active vectors and 2null vectors. The cases for switching of the dual VSI are generated through the SVMPWM strategy, where the phase shift in the switching situations of the inverter VSI-b is 180 degrees, while the switching states of the VSI-a are achieved in a traditional way. On the other side, each inverter has two switches with their anti-parallel diodes. Moreover, each inverter possesses32 possible switching pulses [4]. As a consequence, as illustrated in Figure 2, there are 30 active vectors and 2null vectors. The cases for switching of the dual VSI are generated through the SVMPWM strategy, where the phase shift in the  On the other side, each inverter has two switches with their anti-parallel diodes. Moreover, each inverter possesses32 possible switching pulses [4]. As a consequence, as illustrated in Figure 2, there are 30 active vectors and 2null vectors. The cases for switching of the dual VSI are generated through the SVMPWM strategy, where the phase shift in the switching situations of the inverter VSI-b is 180 degrees, while the switching states of the VSI-a are achieved in a traditional way. The stator winding voltages of the 5PIM drive are represented as follows: Additionally, the dual VSI system's DC source and switching pulses may be used to determine the output voltages of stator windings in the following ways: The stator winding voltages of the 5PIM drive are represented as follows: Additionally, the dual VSI system's DC source and switching pulses may be used to determine the output voltages of stator windings in the following ways: In fact, the only input voltages needed for a 5PIM drive are sinusoidal voltages. It is common knowledge that coupling inductances have time-varying terms; but, in order to simplify the motor model, this independence must be removed. In order to achieve this, the 5PIM model in the natural basis is subjected to Clark transformation. The matrix [T], which is the foundation for this transformation, is represented as follows: 1 cos(θ) cos(2θ) cos(3θ) cos(4θ) 0 sin(θ) sin(2θ) sin(3θ) cos(4θ) 1 cos(2θ) cos(4θ) cos(6θ) cos(8θ) 0 sin(2θ) sin(4θ) sin(6θ) sin(8θ) It is obvious that based on this adequate transformation, the five-phase drive can be written in α − β and u − z instead of the five components presented in the natural frame such as: 1 cos(θ) cos(2θ) cos(3θ) cos(4θ) 0 sin(θ) sin(2θ) sin(3θ) cos(4θ) 1 cos(2θ) cos(4θ) cos(6θ) cos(8θ) 0 sin(2θ) sin(4θ) sin(6θ) sin(8θ) Thus, the voltage vectors in the stationary frames can be described as follows: where a = exp(j2π/5).

Designed Control Methods
This section discusses the theoretical concept of the RFOC strategy and the BSC technique of the OeW-5PIM topology.

RFOC Method
The goal of the RFOC method is to achieve the control of the 5PIM similar to the DC machine [5,9,16], where the d-q stator currents may be adjusted to provide a decoupling between the motor torque and the rotor flux. Laplace transformation is used to impose the machine's equation in relation to the d-q-x-y frames, yielding [9]: where ω s is the synchronous speed. The 5PIM model can therefore be represented by the block diagram that is illustrated in Figure 3.  The following formulas can be used to express the q-stator current and slip speed: For either direct Park transformation, the angle position ( ) is specified as follows: Figure 4 displays the block diagram of the proposed RFOC approach for the OEW-5PIM structure. As can be observed, the reference currents from the errors of motor speed and rotor flux are provided by the PI controllers. These errors are supplied into the PI controllers' input block, which produces the voltage components in the d-q-x-y frame. The stator voltages generated by the PI controllers are transformed to the α-β frames and thereafter given to the SVM-a and SVM-b blocks, which determines the switching cases of the dual VSI. The terms and shown in Figure 5 are represented by: The following formulas can be used to express the q-stator current and slip speed: For either direct Park transformation, the angle position (θ s ) is specified as follows: Figure 4 displays the block diagram of the proposed RFOC approach for the OEW-5PIM structure. As can be observed, the reference currents from the errors of motor speed and rotor flux are provided by the PI controllers. These errors are supplied into the PI controllers' input block, which produces the voltage components in the d-q-x-y frame. The stator voltages generated by the PI controllers are transformed to the α-β frames and thereafter given to the SVM-a and SVM-b blocks, which determines the switching cases of the dual VSI. The terms e d and e q shown in Figure 5 are represented by:

BSC Method
The fundamental goal of the BSC approach is to convert the equivalent closed-loop system into stable subsystems with order equal one [31,32], which are placed in cascade by the Lyapunov function, which guarantees the stability of each synthesis step [2]. In this paper, the proposed backstepping technique is presented in Figure 5 and it is divided into two steps:

BSC Method
The fundamental goal of the BSC approach is to convert the equivalent closed-loop system into stable subsystems with order equal one [31,32], which are placed in cascade by the Lyapunov function, which guarantees the stability of each synthesis step [2]. In this paper, the proposed backstepping technique is presented in Figure 5 and it is divided into two steps:

BSC Method
The fundamental goal of the BSC approach is to convert the equivalent closed-loop system into stable subsystems with order equal one [31,32], which are placed in cascade by the Lyapunov function, which guarantees the stability of each synthesis step [2]. In this paper, the proposed backstepping technique is presented in Figure 5 and it is divided into two steps: First step: Calculation of the reference stator current: The system must adhere to the specified trajectory for each output variable in the initial phase. This is accomplished by defining the tracking errors of the rotor flux vector and the motor speed by: Then, their derivatives give: .
The primary goal of the necessary control is to guarantee the stability of the rotor flux and rotor speed control loops. Here is the formulation of the first Lyapunov function V 1 related to the tracking errors of rotor speed and the rotor flux vector: Using Equation (13), the derivate of V 1 is described by: .
This can be rewritten as follows: .
Hence, in order to provide stable tracking, K 1 and K 2 should be positive values, which gives: Thus, the stator currents generated by the BSC strategy can be written next as: Second step: Calculation of the reference stator voltage: The reference stator voltages for the entire system are calculated in this step, and the current errors are specified as follows: Then, their derivatives give: Accounting for (1), the stator current errors can be calculated as: The e 1 , e 2 , e 3 , e 4 , e 5 , and e 6 are taken into consideration while defining the new Lyapunov function V 2 for the stability study and are represented as follows: Hence, the derivative of the V 2 is obtained by: By setting (20) into (21), the V 2 can be rewritten as follows: If the quantities within parentheses were selected to be equal to zero, a negative derivative of the V 2 would be obtained, whichmeans: Finally, the following formulae give the stator voltage references as expressions: where, the positive values K 3 , K 4 , K 5 , and K 6 are chosen to provide a quicker dynamic of motor speed, rotor flux, as well as stator currents. The block diagram of the proposed BSC for the OeW-5PIM topology is shown in Figure 6.

SVPWM Strategy
The use of the dual VSI system requires a high number of switching states (2 5 ×2 5 ). As a result, many SVM strategies have been developed for the OeW topology, using a modified idea of conventional modulation. In our study, we used a very simple SVPWM strategy, which was presented previously in [5]. In this block, the reference voltage is divided evenly between the two inverters, i.e., each inverter generates half of the needed voltage. Figure 6 depicts the principle of the dual SVPWM strategy (SVM-a and SVM-b). Backstepping control has recently emerged as one of the most widely used design approaches for large-scale non-linear systems.

Experimental Setup
The experimental setup is presented in Figure 7, and it essentially consists of a DSpace 1103 control board, a hysteresis dynamometer, a5PIM of 2.2 kW, a host computer, four three-phase inverters, adaptation interfaces (15V), a speed sensor, current sensors, and an oscilloscope Yokogawa DL850.

SVPWM Strategy
The use of the dual VSI system requires a high number of switching states (2 5 × 2 5 ). As a result, many SVM strategies have been developed for the OeW topology, using a modified idea of conventional modulation. In our study, we used a very simple SVPWM strategy, which was presented previously in [5]. In this block, the reference voltage is divided evenly between the two inverters, i.e., each inverter generates half of the needed voltage. Figure 6 depicts the principle of the dual SVPWM strategy (SVM-a and SVMb). Backstepping control has recently emerged as one of the most widely used design approaches for large-scale non-linear systems.

Experimental Setup
The experimental setup is presented in Figure 7, and it essentially consists of a d Space 1103 control board, a hysteresis dynamometer, a5PIM of 2.2 kW, a host computer, four three-phase inverters, adaptation interfaces (15 V), a speed sensor, current sensors, and an oscilloscope Yokogawa DL850.

SVPWM Strategy
The use of the dual VSI system requires a high number of switching states (2 5 ×2 5 ). As a result, many SVM strategies have been developed for the OeW topology, using a modified idea of conventional modulation. In our study, we used a very simple SVPWM strategy, which was presented previously in [5]. In this block, the reference voltage is divided evenly between the two inverters, i.e., each inverter generates half of the needed voltage. Figure 6 depicts the principle of the dual SVPWM strategy (SVM-a and SVM-b). Backstepping control has recently emerged as one of the most widely used design approaches for large-scale non-linear systems.

Experimental Setup
The experimental setup is presented in Figure 7, and it essentially consists of a DSpace 1103 control board, a hysteresis dynamometer, a5PIM of 2.2 kW, a host computer, four three-phase inverters, adaptation interfaces (15V), a speed sensor, current sensors, and an oscilloscope Yokogawa DL850.   A Hysteresis Dynamometer HD-815-8NA was mounted on the rotor shaft of the motor to vary the load torque disturbances using a DSP6001 controller. The five-phase stator currents are sensed by a Yokogawa current probe which are connected in series with the inverter terminals and sent to the DSP through its analog boards. The phase voltages produced by the dual VSI system are calculated from the DC-bus voltage and switching states, which results in are duction in the required number of sensors and the cost of the control system. The signal of the real rotor speed is also measured through the 60-bit encoder for comparison purposes with the reference speed. The experimental results of the sensorless control algorithms were obtained by using a numerical oscilloscope (Yokogawa DL850) which was linked to the real-time interface.
In the present application, for validation of the proposed control, it was built under Mat lab/Simulink. Furthermore, this control algorithm was implemented on the DSP-1103 board control to generate the switching states of the dual inverter using Control Desk Manager Software. It is well known that such software presents a perfect graphical interface between Simulink blocks and d SPACE that allows for ensuring the generation of the control signals to control and visualize in real time different signals reflecting the concerned variables as outputs which are related to the Simulink environment (the sensors' output signals).
It is important to clarify that the chosen sampling time applied to the implemented system has an important influence on the quality of the resulting signals and their accuracy. Indeed, in this study, major attention was directed to the phase currents and the developed electromagnetic torque, independently of the type of implemented control algorithms. Indeed, due to the limitations imposed by real-time implementation constraints and the complexity of the used control algorithms, a high value of the sampling time of 80 µ swasapplied without affecting the dynamic quality of the control and the feedback signals' execution, while the transistor switching frequency was kept within 20 kHz. It is important to mention that the simulation results are presented for each control algorithm to prove their effectiveness, whereas the experimental results for the same algorithm are presented for the validation of the obtained results through a simulation and to check their practical effectiveness.

Simulation and Experimental Results
For verification of the benefits of the control algorithms given in this study for ensuring the control of the OeW-5PIM topology, the simulation and experimental results are provided to assess the performance of the suggested control algorithms under various situations such as variable load torque, open-phase faults, and high/low-speed operation. The reference flux value was fixed in all tests to 1 Wb. The 5PIM parameters are given in Table 1.

First Test
To show the feasibility of the proposed control algorithms, the first conducted test was carried out under load torque variation. The reference speed was set to 157 rad/s. Figures 8 and 9 display the numerous simulation results of the control algorithms for BSC and RFOC beside each other. Figure 8 presents the OeW-5PIM performance of the RFOC strategy with the load torque application at t = 2 s: (a) speed responses; (b) speed error; (c) developed torque; and (d) stator currents, while Figure 9 shows the OeW-5PIM performance of the BSC strategy under the same conditions (a) speed responses; (b) speed error; (c) developed torque; and (d) stator currents.

First Test
To show the feasibility of the proposed control algorithms, the first conducted test was carried out under load torque variation. The reference speed was set to 157 rad/s. Figures 8 and 9 display the numerous simulation results of the control algorithms for BSC and RFOC beside each other. Figure 8 presents the OeW-5PIM performance of the RFOC strategy with the load torque application at t=2 s: (a) speed responses; (b) speed error; (c) developed torque; and (d) stator currents, while Figure 9 shows the OeW-5PIM performance of the BSC strategy under the same conditions (a) speed responses; (b) speed error; (c) developed torque; and (d) stator currents.

First Test
To show the feasibility of the proposed control algorithms, the first conducted test was carried out under load torque variation. The reference speed was set to 157 rad/s. Figures 8 and 9 display the numerous simulation results of the control algorithms for BSC and RFOC beside each other. Figure 8 presents the OeW-5PIM performance of the RFOC strategy with the load torque application at t=2 s: (a) speed responses; (b) speed error; (c) developed torque; and (d) stator currents, while Figure 9 shows the OeW-5PIM performance of the BSC strategy under the same conditions (a) speed responses; (b) speed error; (c) developed torque; and (d) stator currents.  The obtained experimental results are exhibited in Figures 10 and 11,where Figure 10 represents the OeW-5PIM performance of the RFOC strategy: (a) speed responses, speed error, and developed torque and (b) stator currents, while Figure 11 shows the OeW-5PIM performance of the BSC strategy: (a) speed responses, speed error, and developed torque and (b) stator currents. These results show the validation of the effectiveness of the obtained simulation results for the designed control algorithms under load torque variation.
(c) (d) Figure 9. Simulation results of the BSC strategy for the OeW-5PIM topology under load torque variation.
The obtained experimental results are exhibited in Figures 10 and 11,where Figure 10 represents the OeW-5PIM performance of the RFOC strategy: (a) speed responses, speed error, and developed torque and (b) stator currents, while Figure 11 shows the OeW-5PIM performance of the BSC strategy: (a) speed responses, speed error, and developed torque and (b) stator currents. These results show the validation of the effectiveness of the obtained simulation results for the designed control algorithms under load torque variation.  (c) (d) Figure 9. Simulation results of the BSC strategy for the OeW-5PIM topology under load torque variation.
The obtained experimental results are exhibited in Figures 10 and 11,where Figure 10 represents the OeW-5PIM performance of the RFOC strategy: (a) speed responses, speed error, and developed torque and (b) stator currents, while Figure 11 shows the OeW-5PIM performance of the BSC strategy: (a) speed responses, speed error, and developed torque and (b) stator currents. These results show the validation of the effectiveness of the obtained simulation results for the designed control algorithms under load torque variation. (a) (b) Figure 11. Experimental results of the BSC strategy for the OeW-5PIM topology under load torque variation. Figure 11. Experimental results of the BSC strategy for the OeW-5PIM topology under load torque variation.

Second Test
To evaluate the effectiveness of the proposed control algorithms of the OeW-5PIM under open-phase faults, a special test was carried out with constant load torque (4 N·m at t = 2 s). Figures 12 and 13 show the simulation results of the control techniques for BSC and RFOC. Figure 12  To evaluate the effectiveness of the proposed control algorithms of the OeW-5PIM under open-phase faults, a special test was carried out with constant load torque (4 N.m at t=2 s). Figures 12 and 13 show the simulation results of the control techniques for BSC and RFOC. Figure 12 presents the OeW-5PIM performance of the RFOC strategy with an open-phase fault at t=3 s: (a) speed responses; (b) speed error; (c) developed torque; and (d) stator currents, while Figure 13 represents the OeW-5PIM performance of the BSC strategy:(a) speed responses; (b) speed error; (c) developed torque; and (d) stator currents.

Second Test
To evaluate the effectiveness of the proposed control algorithms of the OeW-5PIM under open-phase faults, a special test was carried out with constant load torque (4 N.m at t=2 s). Figures 12 and 13 show the simulation results of the control techniques for BSC and RFOC. Figure 12     (c) (d)

Third Test
We sought to evaluate the effectiveness of the suggested control strategies under different speed values. Here, there are three steps for the reference speed change, from 0 to 150 rad/s and 150 rad/s to −150 rad/s. Figures 16 and 17 show the simulation results of the OeW-5PIM's performance for BSC and RFOC during reversal speed. The results present the responses of (a) the speed responses; (b) the speed error; (c) the developed torque; and (d) the stator currents.

Third Test
We sought to evaluate the effectiveness of the suggested control strategies under different speed values. Here, there are three steps for the reference speed change, from 0 to 150 rad/s and 150 rad/s to −150 rad/s. Figures 16 and 17 show the simulation results of the OeW-5PIM's performance for BSC and RFOC during reversal speed. The results present the responses of (a) the speed responses; (b) the speed error; (c) the developed torque; and (d) the stator currents. We sought to evaluate the effectiveness of the suggested control strategies under different speed values. Here, there are three steps for the reference speed change, from 0 to 150 rad/s and 150 rad/s to −150 rad/s. Figures 16 and 17 show the simulation results of the OeW-5PIM's performance for BSC and RFOC during reversal speed. The results present the responses of (a) the speed responses; (b) the speed error; (c) the developed torque; and (d) the stator currents. The experimental results of the OeW-5PIM's performance during reversal speed are presented in Figures 18 and 19: (a) speed response and the developed torque response; and (b) is the five phase stator currents.. These results present the validity of the simula-  The experimental results of the OeW-5PIM's performance during reversal speed are presented in Figures 18 and 19: (a) speed response and the developed torque response; and (b) is the five phase stator currents. These results present the validity of the simulation results for the developed control algorithms even under rotor speed variation.
(c) (d) Figure 17. Simulation results of the BSC strategy for the OeW-5PIM topology under reversal speed.
The experimental results of the OeW-5PIM's performance during reversal speed are presented in Figures 18 and 19: (a) speed response and the developed torque response; and (b) is the five phase stator currents.. These results present the validity of the simulation results for the developed control algorithms even under rotor speed variation. (a) (b) Figure 19. Experimental results of the BSC strategy for the OeW-5PIM topology under reversal speed. (c) (d) Figure 17. Simulation results of the BSC strategy for the OeW-5PIM topology under reversal speed.

Discussion
The experimental results of the OeW-5PIM's performance during reversal speed are presented in Figures 18 and 19: (a) speed response and the developed torque response; and (b) is the five phase stator currents.. These results present the validity of the simulation results for the developed control algorithms even under rotor speed variation. (a) (b) Figure 19. Experimental results of the BSC strategy for the OeW-5PIM topology under reversal speed. Figure 19. Experimental results of the BSC strategy for the OeW-5PIM topology under reversal speed.

Discussion
This part provides a quick comparison of the control approaches discussed in this work. Table 2 shows the brief comparison of several factors discovered by using the experimental and simulation results of the designed control techniques. The comparison is based on many factors, including dynamic behavior, open-phase fault, stability characteristics, design options for the controller, and the implementation complexity.
Dynamic behavior: The motor speed tracks the reference speed with excellent performance while changes in the reference speed and load do not affect the speed tracking. Therefore, the speed error is less when compared to the obtained results in [4,[8][9][10][11][12]29]. It can be said that the obtained results clearly prove the accuracy of the backstepping controller against sudden changes in the specified reference speed and load torque compared to the RFOC technique. At the same time, the torque developed by the motor behaves in a similar way to the controlled systems within an acceptable range of ripples compared to the obtained results in previous research works such as in [5][6][7][8]11,24,26], where it can be observed clearly that the torque amplitude changes according to the speed step changes and load torque variation. Furthermore, the d-q rotor flux demonstrates excellent decoupling between the motor torque and the rotor flux even under reversal speed. On the other side, the amplitudes of the five-phase stator currents increased after the load torque changed. In addition, as shown in the zoomed-in window, these currents have balanced sinusoidal signals.
Open-phase fault: It can be seen that the open-phase fault introduced some small fluctuations in the rotor speed and some fluctuations occur in the form of oscillations in the electromagnetic torque, which are basically directly due to the residual asymmetry at the level of the motor stator circuit.
Stability characteristics: Pole compensation is used for the RFOC technique and Lyapunov stability is used for the BSC strategy in the stability study. Both techniques exhibit steady performance, with BSC showing quicker convergence compared to other techniques such as those presented previously in [2,[30][31][32].
Implementation complexity: Because the PI controller, in contrast to the BSC strategy, only has two controller parameters, the RFOC was simpler to implement and design. As a result, the complexity of the BSC's implementation is substantially higher.

Conclusions
In this paper, different control techniques based on the SVPWM strategy were suggested for the control of the studied motor topology. The superiority and efficacy of the suggested control approaches were investigated through real-time implementation by using the d Space 1103 board. Based on the obtained results in this paper, it can be noted clearly that the proposed non-linear backstepping control using the SVPWM strategy can ensure suitable and competitive control for multiphase motors, especially under the topology presented in this paper. At the same time, it can be said that the proposed control allows for the avoidance of computational complexity burdens, and furthermore, it can be easily implemented using low-cost microcontrollers. Based on these aforementioned advantages, it can be concluded that the proposed solution can be a promising candidate in industrial applications, where high reliability and avoidance of operation interruption are ensured such as in electric vehicles, aerospace vehicles, complex industrial processes, and electric ship propulsion. In addition, the non-linear BSC strategy was compared to the RFOC technique in a wide range of operation modes, where by this comparison demonstrated that the BSC strategy provides excellent performance compared to an RFOC approach in terms of quicker response and rise time. Indeed, high performance and good tracking are provided by the backstepping strategy compared with the other RFOC strategies of OeW-5PIM topology in both dynamic and steady state situations. However, the complexity of implementation for BSC still has drawbacks, making it challenging to adjust the gains of the control scheme. Our future research work will further study the optimized torque control via the backstepping approach using a genetic algorithm for the studied motor topology.