Research on Compound Sliding Mode Control of a Permanent Magnet Synchronous Motor in Electromechanical Actuators

: In order to improve the response speed and disturbance rejection ability of a permanent magnet synchronous motor (PMSM) in an electromechanical actuator (EMA), a compound sliding mode control (CSMC) is proposed. The CSMC consists of a sliding mode controller with a new reaching law and disturbance observer based on a symmetric S-type function. The stability of the CSMC is analyzed using the Lyapunov stability analysis. The effectiveness of the CSMC is conﬁrmed by the Simulink simulation, and experiments were conducted on a semi-physical platform. The results obtained by comparing the CSMC with the proportional integral (PI) control and traditional sliding mode control show that the CSMC has a faster response and stronger disturbance rejection ability and reduces chattering.


Introduction
Electromechanical actuators (EMAs) consist of a motor, a reducer, a driver, a controller, sensors, etc. [1], that can realize linear or rotary motion. EMAs are widely used in aerospace, military, robotics, transportation, equipment processing, and other fields due to their advantages of having high integration, a small size, high precision, and high efficiency [2,3]. Permanent magnet synchronous motors (PMSMs) are commonly used in EMAs because of their simple structure, light weight, high-power density, and good dynamic response [4]. However, PMSMs are nonlinear multivariable strong coupling systems, and their operating performance is easily influenced by unmodeled phenomena, parameter uncertainty, and external load. An EMA servo system requires a fast response and disturbance rejection ability, but the actual work environment is complex: frequent start-stops, continuous load changing, and so on [5,6]. Therefore, the traditional proportional-integral-differential controller cannot meet the requirements of the high performance and high precision control of the PMSM in EMAs. Sliding mode control (SMC) is commonly used in PMSMs control in EMAs due to its simple structure, fast response, strong disturbance rejection ability, insensitivity to model uncertainty, and good robustness [7,8].
The SMC can improve the disturbance rejection ability and optimize the motor performance because of the structural characteristics, but it brings the chattering problem to the servo system, which seriously affects the control performance of the system [9]. Currently, reducing the high-frequency chattering and improving the disturbance rejection ability of the SMC are the research hotspots of researchers. An improved reaching law speed sliding mode controller was proposed by Liu Yangqing [10], and the sigmoid function was used to replace the switching function, which effectively reduced the chattering of the SMC and improved the response speed. However, the influence of external load disturbance was not considered. Based on the traditional exponential reaching law, Lin Chengmei [11] introduced a variable exponential function and a hyperbolic tangent function to improve the reaching speed and disturbance rejection ability. Zhou Yang [12] studied a new exponential reaching law with strong adaptive ability. The constant speed term was improved to the time variable, which solved the problem of the slow convergence of the traditional exponential reaching law system. The saturation function of the variable boundary layer was also used to replace the switching function, which reduced chattering. Yan Hongliang [13] proposed an improved reaching law sliding mode speed controller for a time-varying disturbance environment, which improved the dynamic performance of the system and reduced chattering. Moreover, the reaching law had no other parameters, which avoided the difficulty of parameter tuning. Xiong Hualiang [14] designed a supertwisting speed sliding mode controller to replace the q-axis PI controller, and changed the SGN function into a continuous sign function to suppress the torque and speed ripple. Zhou Caijin [15] designed a fractional sliding mode controller for a PMSM speed control system. The fractional order reaching law was used to suppress chattering. The simulation and experimental results showed that a faster response and better stability was achieved. Based on the traditional sliding mode observer, the sigmoid function was introduced as the switching function by Wu Dinghui [16], whereas the variable sliding mode gain method was used to reduce the high-frequency chattering. The tracking and disturbance rejection ability of the controller were verified using experiments. Although the above methods improve the response ability of the system and weaken the sliding mode chattering, they do not consider the influence of the external load disturbance and internal uncertainty of the system. The EMA servo system should have good stability, a good tracking performance, a short settling time, and a strong disturbance rejection ability, etc. However, external load disturbances and internal uncertainties affect the stability of the EMA. Therefore, a disturbance observer should be introduced to estimate the disturbance and reduce its impact [17]. Yong-chao Liu [18,19] proposed a second-order sliding mode controller based on a Hermite neural network. In the speed loop, a disturbance observer based on the HNN was used to compensate both the external disturbance and internal parameter uncertainty. At the same time, a complementary sliding mode speed controller based on a disturbance observer was also proposed. A good tracking performance and high robustness were achieved by both methods. Chen Dai [20] designed a new current-constrained controller, and used the disturbance observer to estimate the mismatched disturbance. Lizhi Qu [21] proposed a sliding mode speed controller based on an extended state observer for the speed tracking control of a PMSM drive system under different disturbances. Zhu Dehong [22] studied a sliding mode controller based on a new variable exponential multi-power reaching law, and designed a new extended sliding mode disturbance observer to estimate the disturbance, which was then fed forward to the sliding mode controller. The results showed that the influence of the system disturbance was eliminated. To solve the problem of disturbance, an adaptive inversion sliding mode controller based on a nonlinear disturbance observer was designed by Lou Peibin [23]. The switching gain was adjusted using the adaptive law to reduce the chattering of the system and improve the disturbance rejection ability. An integral sliding mode controller was designed by Li Zheng [24] to eliminate the steady-state error. The load torque observer was designed according to the principle of the Luenberger linear observer, and the observed value of the sliding mode controller was recorded. However, there was difficulty in selecting the integral initial value, and the disturbance rejection ability was low. Furthermore, Zhao Feng [25] proposed a new reaching law based on a piecewise function to reduce the sliding mode chattering, and observed the motor disturbance using the extended state observer (ESO). The disturbance observation value was compensated as a feedforward signal to the sliding mode controller, which effectively reduced the sliding mode chattering and improved the accuracy of the torque estimation. However, the controller's parameter setting is complex and difficult. In this paper, a SMC is proposed for the speed control of PMSMs to improve the overall performance of the EMA servo system. This approach aims at meeting requirements of the fast response and strong disturbance rejection ability of the PMSM in EMAs. A new reaching law is designed to reduce chattering in the SMC, where the symbol function in the traditional SMC is replaced with the symmetric S-type function. A symmetric Stype function disturbance observer (SSFDO) is designed to observe the uncertainties in PMSMs, such as the external load disturbance and internal parameter uncertainty. In order to suppress the speedy fluctuation caused by the disturbance and the chattering of the controller and to improve the disturbance rejection ability of the system, the observed value as a feedback signal is compensated to the new sliding mode controller to form a compound SMC (CSMC). The stability of the CSMC is analyzed using the Lyapunov equation. Both the simulation and experimental of the motor speed control and disturbance observations were conducted using the MATLAB/Simulink simulation and a semi-physical platform, which proves the feasibility of the combination method of a SMC and a disturbance observer.

Mathematical Model of PMSMs
The core design of an EMA is the PMSM control method. To simplify the analysis, it is assumed that the three-phase PMSM has a symmetrical current, and the core saturation, eddy current, and hysteresis losses can be ignored. Then, the stator voltage equation in the d-q synchronous rotating coordinate system is [26] the electromagnetic torque equation is [26] and the mechanical motion equation is [26] J d dt The parameters u d and u q are the voltage components and i d and i q are the current components of the d-q axis, respectively. R is the stator resistance, and L d and L q are the inductance components of the d-q axis. ϕ f and ω e are the stator flux linkage and angular velocity of the motor, respectively. ω is the mechanical angular velocity of the motor. T e is electromagnetic torque. P n is the pole number of the motor. T L is the load. B is the damping coefficient. J is the rotational inertia of the rotor.
If the PMSM has a surface-mounted rotor, then L d = L q = L. Additionally, when the the field-oriented control method with i d = 0 is used, the mathematical model of the PMSM can be expressed as follows:

Design of a Traditional Sliding Mode Controller
The SMC is a nonlinear control method with a variable structure. The nonlinear control means that the state is discontinuous. The variable structure means that the controller output is changed according to the current state of the system, so that the state vector moves along the predefined state trajectory. In Figure 1, the AB section is the reaching phase, which means that the system state continuously approaches the sliding surface from any position away from the sliding surface and arrives within a certain time. The BC section is the sliding phase, where the system state moves along the sliding surface to the Energies 2021, 14, 7293 4 of 17 equilibrium point. Therefore, the design of a sliding mode controller includes the selection of the sliding surface and the design of the reaching law. These designs are independent of the parameters and disturbances of a servo system; thus, the SMC is highly robust. output is changed according to the current state of the system, so that the state vector moves along the predefined state trajectory. In Figure 1, the AB section is the reaching phase, which means that the system state continuously approaches the sliding surface from any position away from the sliding surface and arrives within a certain time. The BC section is the sliding phase, where the system state moves along the sliding surface to the equilibrium point. Therefore, the design of a sliding mode controller includes the selection of the sliding surface and the design of the reaching law. These designs are independent of the parameters and disturbances of a servo system; thus, the SMC is highly robust. In a traditional sliding mode speed controller, a differential sliding mode surface is generally adopted, and the function is as follows: where, , greater than 0, is the parameter to be designed. The exponential reaching law [27] is generally used as: The speed tracking error of the PMSM is defined as: where is the reference angular velocity and is the actual angular velocity of the motor. According to the mathematical model of the PMSM, the first and second order derivatives of are: Therefore, according to Equations (6) and (9), the output of the traditional sliding mode controller is: In a traditional sliding mode speed controller, a differential sliding mode surface is generally adopted, and the function is as follows: where, c, greater than 0, is the parameter to be designed. The exponential reaching law [27] is generally used as: The speed tracking error of the PMSM is defined as: where ω ref is the reference angular velocity and ω is the actual angular velocity of the motor. According to the mathematical model of the PMSM, the first and second order derivatives of x are: Denote D = 1.5P n ϕ f J and u = di q dt , then the derivative of Equation (5) is combined with Equation (8) to obtain: Therefore, according to Equations (6) and (9), the output of the traditional sliding mode controller is:

Reaching Law Design Based on New Symmetric S-Type Function
Fast reaching and low chattering cannot be considered at the same time in a traditional sliding mode controller with exponential reaching law. Therefore, by combining the exponential and power reaching laws, the new reaching law is obtained: where s is a sliding surface function. ε, k, a, and b are the parameters to be designed. x is the system state variable, which represents the difference between the actual speed and the reference speed.
Energies 2021, 14, 7293 5 of 17 When the system state point is far from the sliding surface, s and x are large, and the new reaching law can be rewritten as Equation (12). Consequently, the state point moves toward the sliding surface with the combination speed of the two items.
When the system state point is close to the sliding surface, s and x are very small, and the new reaching law can be expressed as Equation (13). The variable exponent term reaches zero, and the variable speed term dominates the movement of the state.
With SMC, the system state point moves to the origin along the sliding surface and finally stabilizes at the origin. Therefore, the variable speed term decreases continuously in this process so that the system state point will not have a high-frequency oscillation near the sliding surface due to the velocity inertia. The system chattering is reduced.
The symbolic function sgn(s) is a discontinuous switching function, which switches instantaneously near the zero point. Therefore, high-frequency chattering is generated when the system state point moves along the sliding surface. In order to improve the disturbance rejection ability and reduce the chattering of the controller, this study uses the continuous symmetric S-type function instead of the symbolic function. The symmetric S-type function equation is as follows where α > 0, and its value determines how fast the value of the symmetric S-type smooth function changes near the origin. The switch and symmetric S-type function are shown in Figure 2. When α is infinite, f(s) can be converted to a switch function, which can cause large chattering. When α is very small, the boundary layer thickness is large, the system convergence is slow, and the robustness is poor. To meet the requirements of the high precision and good robustness of the system, α = 2 is selected in the study. This maintains the switching characteristics of SMC and effectively reduces the discontinuity of the system, thereby reducing the chattering and improving the disturbance rejection ability.
is the system state variable, which represents the difference between the actua and the reference speed.
When the system state point is far from the sliding surface, and are lar the new reaching law can be rewritten as Equation (12). Consequently, the stat moves toward the sliding surface with the combination speed of the two items.
When the system state point is close to the sliding surface, and are very and the new reaching law can be expressed as Equation (13). The variable expone reaches zero, and the variable speed term dominates the movement of the state.
With SMC, the system state point moves to the origin along the sliding surf finally stabilizes at the origin. Therefore, the variable speed term decreases contin in this process so that the system state point will not have a high-frequency osc near the sliding surface due to the velocity inertia. The system chattering is reduce The symbolic function sgn( ) is a discontinuous switching function, which s instantaneously near the zero point. Therefore, high-frequency chattering is ge when the system state point moves along the sliding surface. In order to improve turbance rejection ability and reduce the chattering of the controller, this study u continuous symmetric S-type function instead of the symbolic function. The symm type function equation is as follows where α > 0, and its value determines how fast the value of the symmetric S-type function changes near the origin. The switch and symmetric S-type function are sh Figure 2. When α is infinite, f( ) can be converted to a switch function, which ca large chattering. When α is very small, the boundary layer thickness is large, the convergence is slow, and the robustness is poor. To meet the requirements of th precision and good robustness of the system, α = 2 is selected in the study. This ma the switching characteristics of SMC and effectively reduces the discontinuity of tem, thereby reducing the chattering and improving the disturbance rejection abil  Therefore, the new reaching law based on the symmetric S-type function is shown in Equation (15), where ε > 0, k > 0, a, b ∈ [0, 1], and α = 2.

Design of a New Sliding Mode Controller and Its Stability Analysis
The new sliding mode controller can be obtained from Equations (9) and (15) as and the reference current of q-axis can be obtained by integrating Equation (16) as To verify the stability of the system, the Lyapunov function is built as follows [28] whereas the derivative of V is obtained by combining Equation (15) .
V ≤ 0. Based on the stability theory, the new SMC system proposed in this study can converge to a stable state in finite time.

Design of Symmetric S-Type Function Disturbance Observer
Here, a differential sliding surface is used. In the second derivative of the velocitytracking error, the influence of external load disturbance is ignored. However, the external load is variable in the practical application of EMAs. The ignorance of the external load will lead to the oscillation of the EMA output, which should be avoided. Therefore, it is necessary to design an observer to observe the external load and feedforward compensation to the new sliding mode controller. By introducing such a design, the performance of the SMC, stability of the EMA operation, and control accuracy are improved.
The sampling frequency of the controller is usually much greater than the change time of the load torque, so the load torque can be considered a constant value in a sampling period; that is, . T L = 0. Combined with the mechanical motion and electromagnetic torque equations of PMSMs, the motor angular velocity ω and the load torque T L are designed as state variables. The q-axis current is used as an input, and the estimated angular velocity and observed load torque are used as outputs. Therefore, the state space and disturbance observer equations of PMSMs are shown in Equations (20) and (21), respectively where,ω is the estimated motor angular velocity;T L is the observed load torque; l is the feedback gain of the disturbance observer; U is the SMC rate, which is defined as U = −βf(s) − γs, where β and γ are the gains of the SMC rate; s is the sliding surface; and f(s) is the symmetric S-type function. Subtracting Equation (20) from Equation (21), the error equations of the observer become.
. In Equation (22), e 1 and e 2 are the speed estimation and load torque observation error, respectively. The sliding mode switching surface s = e 1 = 0 is defined. From the sliding mode accessibility condition, s . s ≤ 0, which can be obtained as In Equation (23), γ > 0 and λ ≥ |e 2 | J > 0. When the system state point reaches the sliding surface and moves along the sliding surface, e 1 = 0. Substituting Equation (22) into Equation (23), we have where h is a constant. As long as the value of l is less than 0, e 2 ≈ 0; then, the load torque can be observed. Based on the above analysis, the structural diagram of the SSFDO is shown in Figure 3.
In Equation (22), are the speed estimation and load torq ror, respectively. The sliding mode switching surface = = 0 is def ing mode accessibility condition, s ≤ 0, which can be obtained as In Equation (23) where ℎ is a constant. As long as the value of is less than 0, ≈ 0; th can be observed. Based on the above analysis, the structural diagram shown in Figure 3.

Design of Compound Sliding Mode Controller Based on SSFDO
In this study, the new reaching law and continuous symmetric S used in the new sliding mode controller designed. The speed of the re celerated, the time to reach the steady state is reduced, and the chatter reduced to some extent. However, the influence of the external load d ternal parameter change on the system is ignored. In order to impro rejection ability of the system, the SSFDO is used to observe the change in real time. The observation torque is feedforward compensated mode controller to form a compound sliding mode controller, enhanc and improve the robustness of the system. Finally, the expression of t the SSFDO is shown in Equation (25), whereas the overall system con is shown in

Design of Compound Sliding Mode Controller Based on SSFDO
In this study, the new reaching law and continuous symmetric S-type function are used in the new sliding mode controller designed. The speed of the reaching phase is accelerated, the time to reach the steady state is reduced, and the chattering of the system is reduced to some extent. However, the influence of the external load disturbance and internal parameter change on the system is ignored. In order to improve the disturbance rejection ability of the system, the SSFDO is used to observe the change in load disturbance in real time. The observation torqueT L is feedforward compensated to the new sliding mode controller to form a compound sliding mode controller, enhance the control effect, and improve the robustness of the system. Finally, the expression of the CSMC based on the SSFDO is shown in Equation (25), whereas the overall system control block diagram is shown in Figure 4.
ing mode accessibility condition, s ≤ 0, which can be obtained as In Equation (23), > 0 and ≥ | | > 0. When the system state poin sliding surface and moves along the sliding surface, = 0. Substituting into Equation (23), we have where ℎ is a constant. As long as the value of is less than 0, ≈ 0; then, th can be observed. Based on the above analysis, the structural diagram of shown in Figure 3.

Design of Compound Sliding Mode Controller Based on SSFDO
In this study, the new reaching law and continuous symmetric S-type used in the new sliding mode controller designed. The speed of the reachin celerated, the time to reach the steady state is reduced, and the chattering of reduced to some extent. However, the influence of the external load distur ternal parameter change on the system is ignored. In order to improve th rejection ability of the system, the SSFDO is used to observe the change in loa in real time. The observation torque is feedforward compensated to th mode controller to form a compound sliding mode controller, enhance the and improve the robustness of the system. Finally, the expression of the CS the SSFDO is shown in Equation (25), whereas the overall system control b is shown in

Simulation and Experimental Results Analysis
In order to verify the feasibility of the compound sliding mode controller, both the simulation and experimental verification were carried out using the MATLAB/Simulink simulation and the Links-RT-PMSM servo platform. The parameters of the PMSM and the test bed are shown in Table 1.

Analysis of Simulation Results
The system simulation model is shown in Figure 5. The simulation time of the system is set as 0.4 s, and the sampling period is set as 10 µs. The control strategy with i d = 0 is adopted, and the results of the CSMC are compared with the traditional SMC and the PI control. simulation and the Links-RT-PMSM servo platform. The parameters of the P test bed are shown in Table 1.

Analysis of Simulation Results
The system simulation model is shown in Figure 5. The simulation time is set as 0.4 s, and the sampling period is set as 10 μs. The control strategy adopted, and the results of the CSMC are compared with the traditional SM control.  Figure 6, where TL is the given torque waveform and TL1 is th torque waveform. Figure 6a shows the response time when the observation t the given torque value. Figure 6b shows the fluctuation of the observed tor ging torque is caused by the special structure of the PMSM motor, which observed torque. Based on the annotation of (a) in Figure 6, the converge 0.005 s and convergence rate is fast. It can be seen from Figure 6b that t amplitude range is between 0.001 N • m, the waveform oscillation is sma servation accuracy is high.

Simulation Analysis of SSFDO
In order to verify the observation effect of the load disturbance observer, the motor is set to start without the load and the 5 N·m load torque is suddenly applied at t = 0.2 s. The gain values in SSFDO are β = 2, γ = 4000, and l = −4. The observation results are shown in Figure 6, where TL is the given torque waveform and TL1 is the observation torque waveform. Figure 6a shows the response time when the observation torque reaches the given torque value. Figure 6b shows the fluctuation of the observed torque. The cogging torque is caused by the special structure of the PMSM motor, which fluctuates the observed torque. Based on the annotation of (a) in Figure 6, the convergence time ∆t = 0.005 s and convergence rate is fast. It can be seen from Figure 6b that the fluctuation amplitude range is between ±0.001 N·m, the waveform oscillation is small, and the observation accuracy is high.  Figure 7, the speed change in the new SMC with or withou turbance is compared. "New-SMC" represents the speed change cu of the new sliding mode controller designed, whereas "SSFDO-C speed curve under the compound sliding mode controller with th function disturbance observer. Figure 7a shows the starting perform tor and Figure 7b shows the disturbance rejection ability of the mot Furthermore, Figure 7a shows that the startup performance of t regardless of the addition of the observation disturbance. It shoul the rise time = 0.011 s, the maximum speed is 1036 rpm and the 0.029 s. It can be seen from Figure 7b that, after the load torque i controlled by the new sliding mode controller decreases to 990.7 rp cover to stability is = 0.002 s. The speed controlled by the com controller is reduced to 994.8 rpm, and the time to recover to stab Based on the above analysis, adding the observed disturbance can caused by the load change and quicken the recovery time. In Figure 7, the speed change in the new SMC with or without the observation disturbance is compared. "New-SMC" represents the speed change curve under the control of the new sliding mode controller designed, whereas "SSFDO-CSMC" represents the speed curve under the compound sliding mode controller with the symmetrical S-type function disturbance observer. Figure 7a shows the starting performance curve of the motor and Figure 7b shows the disturbance rejection ability of the motor.  Figure 7, the speed change in the new SMC with or withou turbance is compared. "New-SMC" represents the speed change cu of the new sliding mode controller designed, whereas "SSFDO-C speed curve under the compound sliding mode controller with th function disturbance observer. Figure 7a shows the starting perform tor and Figure 7b shows the disturbance rejection ability of the mot Furthermore, Figure 7a shows that the startup performance of t regardless of the addition of the observation disturbance. It shoul the rise time = 0.011 s, the maximum speed is 1036 rpm and the 0.029 s. It can be seen from Figure 7b that, after the load torque i controlled by the new sliding mode controller decreases to 990.7 rp cover to stability is = 0.002 s. The speed controlled by the com controller is reduced to 994.8 rpm, and the time to recover to stab Based on the above analysis, adding the observed disturbance can caused by the load change and quicken the recovery time.

Simulation Analysis of the Startup Performance and Disturba
The target speed is set to 1000 rpm. The speed and current l compound sliding mode, traditional sliding mode, and PI controll Table 2. Furthermore, Figure 7a shows that the startup performance of the motor is consistent, regardless of the addition of the observation disturbance. It should be noted that when the rise time t r = 0.011 s, the maximum speed is 1036 rpm and the adjustment time t a = 0.029 s. It can be seen from Figure 7b that, after the load torque is increased, the speed controlled by the new sliding mode controller decreases to 990.7 rpm and the time to recover to stability is t s1 = 0.002 s. The speed controlled by the compound sliding mode controller is reduced to 994.8 rpm, and the time to recover to stability is t s2 = 0.0014 s. Based on the above analysis, adding the observed disturbance can reduce the chattering caused by the load change and quicken the recovery time.

Simulation Analysis of the Startup Performance and Disturbance Rejection Ability
The target speed is set to 1000 rpm. The speed and current loop parameters of the compound sliding mode, traditional sliding mode, and PI controller are set as shown in Table 2. Table 2. Gain parameters of three control methods.

Control Methods Speed Loop Current Loop
PI control K p = 0.14 In the CMSC, a = 0.1 and b = 0.02. Figure 8a shows the multiple of the speed reduction of the system point in the sliding phase under the CSMC. Figure 8b shows the multiple of the speed increase of the system point in the reaching phase under the CMSC. As shown in Figure 8, compared with the traditional exponential reaching law SMC, when the system point is far away from the sliding surface, say, x 0, the speed of the CSMC in the reaching motion stage increases by 1.1-2 times. When the system point reaches the sliding surface, say, x ≈ 0, the speed of the CSMC in the sliding mode stage decreases by 0-0.6 times. Therefore, the selection of a and b values meets the requirements of the acceleration of the system point in the reaching motion stage and deceleration in the sliding mode stage, which makes it difficult to cause the system chattering. In the CMSC, a = 0.1 and b = 0.02. Figure 8a show of the system point in the sliding phase under the CSM the speed increase of the system point in the reaching in Figure 8, compared with the traditional exponenti tem point is far away from the sliding surface, say, reaching motion stage increases by 1.1-2 times. When surface, say, ≈ 0, the speed of the CSMC in the sli times. Therefore, the selection of a and b values meets of the system point in the reaching motion stage an stage, which makes it difficult to cause the system ch The starting speed performance and disturbance lated using the above three control methods. The sp Figure 9a shows the starting speed performance curv The starting speed performance and disturbance rejection ability of PMSM are simulated using the above three control methods. The speed changes are shown in Figure 9. Figure 9a shows the starting speed performance curve of the motor and Figure 9b shows the disturbance rejection ability of the motor. lated using the above three control methods. The speed c Figure 9a shows the starting speed performance curve of t the disturbance rejection ability of the motor.   Figure 9a shows that the speed rise under the PI control is the largest, whereas the rise time and time to recover to the steady state are longer. The speed overshoot of the traditional SMC is greater than that of the CSMC, and the time to recover to the steady state is longer than that of the CSMC under the same rise time. Furthermore, Figure 9b shows that, under the same load disturbance, the CSMC has the smallest chattering and shortest recovery time, whereas the PI control has the largest chattering and longest recovery time. This shows that the disturbance rejection ability of the CSMC is strong.
Further, the motor is started without a load and the load step is suddenly added after a certain time. The motor speed overshoot, speed change in the disturbance rejection ability, and adjustment time of the three control methods are shown in Table 3. According to the data comparison in Table 3, the proposed CSMC designed is significantly better than the PI control and traditional SMC in the motor startup performance and disturbance rejection. In the simulation, the initial speed was set to 1000 rpm, and a constant torque of 5 N·m was applied. Then, the speed was changed step by step, first decreasing from 1000 rpm to 500 rpm, then increasing to 800 rpm, 1000 rpm, 1100 rpm, and finally returning to 1000 rpm. The simulation results are shown in Figure 10. Figure 10a shows the starting speed performance curve of the motor and Figure 10b shows the disturbance rejection ability of the motor. Figure 10c-e shows the starting speed performance of the motor at different step speeds. performance curve of the motor and Figure 10b shows the disturb the motor. Figure 10c-e shows the starting speed performance o step speeds. The results in Figure 10 show that the CSMC has the best track the speed step with a constant torque of 5 N • m. Compared with t tional SMC, the CSMC can reach the target speed quickly and wit The results in Figure 10 show that the CSMC has the best tracking performance under the speed step with a constant torque of 5 N·m. Compared with the PI control and traditional SMC, the CSMC can reach the target speed quickly and without overshoot.

Analysis of the Experimental Results
The servo control platform is shown in Figure 11. The no-load and on-load experiments under the PI control, traditional SMC, and CSMC are conducted on the servo platform. The execution frequencies of the current and speed loops are 10 KHz and 1 KHz, respectively, and the frequency of the recorded data is 1 KHz.

Analysis of the Experimental Results
The servo control platform is shown in Figure 11. The no-load and on-load experiments under the PI control, traditional SMC, and CSMC are conducted on the servo platform. The execution frequencies of the current and speed loops are 10 KHz and 1 KHz, respectively, and the frequency of the recorded data is 1 KHz.

Experimental Verification of SSFDO
The actual effect of the disturbance observer is verified by brake loading. In the actual test, the gain values of SSFDO are = 0.01, = 3, and = −0.02, whereas the observation effect of the load disturbance is shown in Figure 12. Figure 12a-c show the response time and fluctuation of the observed torque when the observed torque reaches different given torque values. The motor is set to start without a load, and the current of 0.1 A is suddenly loaded at 1.8 s and unloaded at 3.6 s. It can be seen from Figure 12a that the torque observed by the observer is 0.112 N • m. Then, the 0.2 A current is suddenly loaded at 4.9 s and unloaded at 7 s. Figure 12b shows that the torque observed by the observer is 0.215 N • m. Figure 12c shows that there is a disturbance of 0.023 N • m when there is no load.
The torque values observed in Figure 12 are consistent with those in the standard torque characteristic curve. When the current increases twice, the torque also increases twice. The convergence and recovery time are ∆t = 0.5 s, and the fluctuation amplitude is between 0.001 N • m. Therefore, the SSFDO designed in this study has a high observation accuracy and practical significance.

Experimental Verification of SSFDO
The actual effect of the disturbance observer is verified by brake loading. In the actual test, the gain values of SSFDO are β = 0.01, γ = 3, and l = −0.02, whereas the observation effect of the load disturbance is shown in Figure 12. Figure 12a-c show the response time and fluctuation of the observed torque when the observed torque reaches different given torque values. The motor is set to start without a load, and the current of 0.1 A is suddenly loaded at 1.8 s and unloaded at 3.6 s. It can be seen from Figure 12a that the torque observed by the observer is 0.112 N·m. Then, the 0.2 A current is suddenly loaded at 4.9 s and unloaded at 7 s. Figure 12b shows that the torque observed by the observer is 0.215 N·m. Figure 12c shows that there is a disturbance of 0.023 N·m when there is no load.
twice. The convergence and recovery time are ∆t = 0.5 s, an between 0.001 N • m. Therefore, the SSFDO designed in tion accuracy and practical significance. The comparison of the actual test of the speed changes and the new SMC is shown in Figure 13. It can be seen fro The torque values observed in Figure 12 are consistent with those in the standard torque characteristic curve. When the current increases twice, the torque also increases twice. The convergence and recovery time are ∆t = 0.5 s, and the fluctuation amplitude is between ±0.001 N·m. Therefore, the SSFDO designed in this study has a high observation accuracy and practical significance.
The comparison of the actual test of the speed changes in the CSMC based on SSFDO and the new SMC is shown in Figure 13. It can be seen from Figure 13a that the startup performance of the motor is identical whether the observation disturbance is added or not. As shown in Figure 13b, when the current load is increased by 0.1 A at 5.04 s, the chattering caused by the CSMC is smaller than that of the new SMC, and the time to recover to stability is faster. The experimental and simulation results are shown in Table 4. Based on the comparison of data with and without the observer in Table 4, it is proven that the proposed CSMC is effective.

1, 14, x FOR PEER REVIEW
performance of the motor is identical whether the observa not. As shown in Figure 13b, when the current load is inc chattering caused by the CSMC is smaller than that of the n cover to stability is faster. The experimental and simulation Based on the comparison of data with and without the obs that the proposed CSMC is effective.    The target speed is set to 1000 rpm, and the load torque corresponding to 0.1 A is loaded at 5.0 s. The parameter settings of the speed and current loops of the three control methods are shown in Table 5. The speed changes in the three control methods under the same load are shown in Figure 14. Figure 14a shows the starting speed performance curve of the motor and Figure 14b shows the disturbance rejection ability of the motor. Table 5. Gain parameters of three control methods in the experimental test.

Control Methods Speed Loop Current Loop
PI control K p = 0.02  Figure 14a shows that, under the same rise time, the over smallest, whereas the adjustment time is the shortest. Figure 1 Figure 14a shows that, under the same rise time, the overshoot of the CSMC is the smallest, whereas the adjustment time is the shortest. Figure 14b shows that, when the same torque is loaded, the chattering of the CSMC is the smallest and the time to recover up to the steady state is the shortest. The motor speed overshoot, rapid change in the disturbance rejection ability, and adjustment time of the three control methods are shown in Table 6. The authenticity of the simulation results is verified by comparing the data in Table 6. It is again proven that the CSMC designed in this study is significantly better than the PI control and traditional SMC in the motor startup performance and disturbance rejection ability. In the experimental tests, the initial speed was set to 1000 rpm, and a constant torque of 0.112 N·m was applied. Then, the speed was changed step by step, first decreasing from 1000 rpm to 500 rpm, then increasing to 800 rpm, 1000 rpm, and 1100 rpm, and finally returning to 1000 rpm. The simulation results are shown in Figure 15. Figure 15a shows the starting speed performance curve of the motor and Figure 15b shows the disturbance rejection ability of the motor. Figure 15c-e shows the starting speed performance of the motor at different step speeds. The results in Figure 15 show that the CSMC has the be the speed step with a constant torque of 0.112 N • m. Com traditional SMC, the CSMC can reach the target speed quic The results in Figure 15 show that the CSMC has the best tracking performance under the speed step with a constant torque of 0.112 N·m. Compared with the PI control and traditional SMC, the CSMC can reach the target speed quickly and without overshoot.

Conclusions
A CSMC based on SSFDO is proposed in this study for the control of PMSMs in EMAs. A new reaching law and disturbance observation feedforward compensation method are adopted by the controller to improve the response and disturbance rejection ability of the system. The stability is judged by the Lyapunov stability criterion, and the simulation and experimental verification are conducted using the Simulink and semi-physical platform. From the simulation and experimental results, it can be concluded that the performance, such as the overshoot, settling time, and disturbance rejection ability of the CSMC, was greatly improved compared with the PI controller and traditional SMC. The simulation and experimental results are consistent, indicating the effectiveness and superiority of the CSMC. However, in this paper, only the disturbance rejection ability of the CSMC under step load disturbance was studied. The disturbance rejection ability of the CSMC under continuous disturbance should also be further studied. Moreover, the effectiveness of the CSMC under different speeds should be further studied.